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mga-53543 50 mhz to 6 ghz high linear amplifer data sheet description avago technologiess mga-53543 is a high dynamic range low noise amplifer mmic housed in a 4-lead sc - 70 (sot- 343) surface mount plastic package. the combination of high linearity, low noise fgure and high gain makes the mga-53543 ideal for cellular/pcs/ w-cdma base stations, wireless lan, wll and other systems in the 50 mhz to 6 ghz frequency range. mga-53543 is especially ideal for cellular/pcs/ w - cdma basestation applications. with high ip3 and low noise fgure, the mga-53543 may be utilized as a driver ampli - fer in the transmit chain and as a second stage lna in the receive chain. surface mount package sot-343/4-lead sc70 features ? lead-free option available ? very high linearity at low dc bias power [1] ? low noise fgure ? advanced enhancement mode phemt technology ? excellent uniformity in product specifcations ? low cost surface mount small plastic package sot- 343 (4-lead sc-70) ? tape-and-reel packaging option available specifcations 1.9 ghz, 5v, 54 ma (typ) ? oip3: 39 dbm ? noise fgure: 1.5 db ? gain: 15.4 db ? p-1db: 18.6 dbm applications ? base station radio card ? high linearity lna for base stations, wll, wlan, and other applications in the 50 mhz to 6 ghz range note: 1. the mga-53543 has a superior lfom of 15 db. linearity figure of merit (lfom) is essentially oip3 divided by dc bias power. there are few devices in the market that can match its combination of high linearity and low noise fgure at the low dc bias power of 5v/54 ma. pin connections and package marking simplifed schematic b i a s i n p u t g n d o u t p u t , v d note: top view. package marking provides orientation and identifcation. 53 = device code x = date code character identifes month of manufacture. 53x gnd input output & v d gnd 3 4 1 2 attention: observe precautions for handling electrostatic sensitive devices. esd machine model (class a) esd human body model (class 1a) refer to avago application note a004r: lectrostatic discharge damage and control.
mga-53543 absolute maximum ratings [1] symbol parameter units absolute maximum v in maximum input voltage v 0.8 v d supply voltage v 5.5 p d power dissipation [] mw 400 p in cw rf input power dbm 13 t j junction temperature c 150 t stg storage temperature c -65 to 150 thermal resistance [3] (vd=5.0v) q jc = 130 c/w notes: 1. operation of this device in excess of any of these limits may cause permanent dam - age. . source lead temperature is 5c. derate 7.7mw/c for t l > 98c 3. thermal resistance measured using 150c liquid crystal measurement technique. electrical specifcations t c = +5c, z o = 50 ?, v d = 5v, unless noted symbol parameter and test condition frequency units min. typ. max. [3] i d current drawn n/a ma 40 54 70 .7 nf [1] noise figure .4 ghz 1.9 1.9 ghz db 1.5 1.9 0.06 0.9 ghz 1.3 gain [1] gain .4 ghz 15.1 1.9 ghz db 14 15.4 17.0 0.5 0.9 ghz 17.4 oip3 [1,] output third order intercept point .4 ghz 38.7 1.9 ghz dbm 36 39.1 1.89 0.9 ghz 39.7 p1db [1] output power at 1 db gain compression .4 ghz 18.3 1.9 ghz dbm 18.6 0.9 ghz 19.3 pae [1] power added efciency at p1db 1.9 ghz % 9.7 0.9 ghz % 8.3 rl in [1] input return loss .4 ghz -1.7 1.9 ghz db -13. 0.9 ghz -11.1 rl out [1] output return loss .4 ghz -5.1 1.9 ghz db -14.3 0.9 ghz -14.4 isol [1] isolation |s 1 | 1.9 ghz db -3.4 0.9 ghz -.3 notes: 1. measurements obtained from a test circuit described in figure 1. input and output tuners tuned for maximum oip3 while keeping vswr bet - ter than :1. data corrected for board losses. . i) output power level and frequency of two fundamental tones at 1.9 ghz: f1 = 5.49 dbm, f = 5.49 dbm, f1 = 1.905 ghz, and f = 1.915 ghz. ii) output power level and frequency of two fundamental tones at 900 mhz: f1 = -0.38 dbm, f = -0.38 dbm, f1 = 905 mhz, and f = 915 mhz. 3. standard deviation data are based on at least 500 pieces sample size taken from 8 wafer lots. future wafers allocated to this product may have nominal values anywhere between the upper and lower spec limits. figure 1. block diagram of 1.9 ghz test fixture. input gamma & transmission line source = 0.38 156 (0.7 dbm loss) rf output rf input v d 53x output gamma & transmission line with bias tee load = 0.05 45 (0.85 dbm loss)
3 mga-53543 typical performance all data measured at t c = 5c, v d = 5 v with input and output tuners tuned for maximum oip3 while keeping vswr better than :1 unless stated otherwise. pout (dbm) figure 3. output third order intercept point vs. output power at 2 ghz. oip3 (dbm) 45 40 35 30 25 20 -5 3 -1 11 15 7 frequency (ghz) figure 4. output power at 1db compression vs. frequency and temperature. 0 7 2 1 4 5 6 3 -40 c +25 c +85 c p1db (dbm) 24 20 16 12 8 frequency (ghz) figure 5. |s 21 | 2 vs. frequency and temperature. 0 2 1 4 5 6 3 -40 c +25 c +85 c |s 21 | 2 (db) 20 15 10 5 frequency (ghz) figure 6. fmin vs. frequency and temperature. 0 2 1 4 5 6 3 -40 c +25 c +85 c fmin (db) 3.8 2.8 1.8 0.8 figure 7. s11 and s22 (50 ? ) vs. frequency. s11 & s22 (db) 0 -5 -10 -15 -20 -25 frequency (ghz) 0 2 1 4 5 6 3 s22 s11 figure 8. isolation vs. frequency. isolation (db) -19 -21 -23 -25 -27 -29 frequency (ghz) 0 2 1 4 5 6 3 s12 v d (v) figure 9. current vs. voltage and temperature. 0 2 1 4 5 6 3 -40 c +25 c +85 c i d (ma) 70 60 50 40 30 20 10 0 frequency (ghz) figure 2. output third order intercept point vs. frequency and temperature. oip3 (dbm) 0 45 40 35 30 25 20 7 2 1 4 5 6 3 -40 c +25 c +85 c
4 mga-53543 typical scattering parameters t c = 5c, v d = 5.0v, i d = 54 ma, z o = 50 ?, (in icm test fxture) freq s 11 s 11 s 21 s 21 s 21 s 12 s 12 s 12 s 22 s 22 k (ghz) mag. ang. db mag. ang. db mag. ang. mag. ang. 0.05 0.83 -38.8 6.6 0.56 161.3 -7.96 0.04 59.7 0.7 -33 0.3 0.1 0.641 -66.7 4.39 16.584 148.9 -4.9 0.061 40.6 0.558 -61.5 0.4 0. 0.439 -98.7 1.55 11.954 14.7 -.50 0.075 .9 0.344 -95.3 0.7 0.3 0.349 -116.8 0.14 10.165 141.8 -.05 0.079 15.4 0.35 -118.3 0.9 0.4 0.305 -18.9 19.39 9.317 140.7 -1.94 0.08 11. 0.176 -138. 0.9 0.5 0.51 -135.6 18.9 8.86 139.3 -1.83 0.081 9 0.097 -167.4 1 0.6 0.33 -14.5 18.6 8.509 136.7 -1.7 0.08 7 0.087 159.7 1 0.7 0. -147.5 18.34 8.61 133.6 -1.7 0.08 5.4 0.094 131.8 1.1 0.8 0.1 -151.1 18.1 8.053 130. -1.7 0.08 4 0.11 110.7 1.1 0.9 0.07 -153.6 17.9 7.854 16.7 -1.6 0.083 .8 0.19 95.4 1.1 1.0 0.01 -155.3 17.7 7.674 13 -1.6 0.083 1.7 0.148 84.1 1.1 1.1 0.198 -157.3 17.51 7.505 119. -1.6 0.083 0.7 0.169 74.8 1.1 1. 0.196 -158. 17.31 7.335 115.4 -1.6 0.083 -0. 0.186 66.6 1.1 1.3 0.194 -158.4 17.1 7.165 111.6 -1.6 0.083 -1.1 0.03 59.6 1.1 1.4 0.195 -159.4 16.9 7 107.7 -1.6 0.083 - 0.19 53.1 1.1 1.5 0.197 -160 16.7 6.836 103.9 -1.6 0.083 -.8 0.35 47.6 1.1 1.6 0.199 -160.1 16.48 6.666 100.1 -1.7 0.08 -3.6 0.48 4. 1.1 1.7 0.01 -160.5 16.6 6.498 96.3 -1.7 0.08 -4.3 0.61 37.1 1.1 1.8 0.05 -161.5 16.04 6.341 9.6 -1.7 0.08 -4.9 0.73 3.4 1.1 1.9 0.1 -16.6 15.8 6.179 88.9 -1.83 0.081 -5.6 0.83 8 1. .0 0.16 -163.1 15.59 6.017 85.3 -1.83 0.081 -6. 0.93 3.8 1. .1 0.1 -164.8 15.36 5.86 81.7 -1.94 0.08 -6.7 0.301 19.8 1. . 0.9 -166.1 15.14 5.714 78.3 -1.94 0.08 -7.3 0.31 16 1. .3 0.35 -167. 14.9 5.56 74.7 -.05 0.079 -7.6 0.316 1.3 1. .4 0.41 -169. 14.67 5.41 71. -.16 0.078 -7.9 0.3 8.8 1.3 .5 0.5 -171.4 14.43 5.65 67.8 -.16 0.078 -8. 0.37 5.5 1.3 3.0 0.93 176.8 13.8 4.611 51.5 -.50 0.075 -8.6 0.338 -9.4 1.4 3.5 0.34 16. 1.13 4.039 36. -.73 0.073 -7.3 0.333 -.6 1.5 4.0 0.394 148. 10.99 3.544 1.6 -.6 0.074 -5.3 0.313 -34.9 1.6 4.5 0.445 133.9 9.84 3.105 7.8 -.7 0.077 -3.4 0.87 -48 1.6 5.0 0.497 11.6 8.7 .71 -5. -1.51 0.084 -.7 0.56 -6.1 1.6 5.5 0.534 109.9 7.56 .388 -17.5 -0.7 0.09 -3.5 0.9 -77.8 1.6 6.0 0.565 99.5 6.46 .105 -8.8 -19.83 0.10 -5.9 0.04 -94.1 1.5 6.5 0.595 88. 5.38 1.857 -39.6 -18.94 0.113 -10.4 0.185 -108.7 1.5 7.0 0.615 77.5 4.31 1.643 -49.8 -18.7 0.1 -16 0.16 -10. 1.5 7.5 0.635 65. 3.3 1.46 -59.6 -17.7 0.13 -.1 0.17 -18.8 1.6 8.0 0.66 53.9 .9 1.301 -68.8 -17.7 0.137 -8. 0.084 -13.9 1.6 8.5 0.68 43.4 1.37 1.171 -77.6 -16.77 0.145 -34. 0.033 -145.4 1.6 9.0 0.715 3.3 0.45 1.053 -86 -16.31 0.153 -40.9 0.08 57.9 1.6 9.5 0.75 4.9 -0.31 0.965 -93.5 -15.86 0.161 -47.5 0.081 51.3 1.5 10.0 0.754 16 -1.1 0.879 -101.7 -15.55 0.167 -55.3 0.19 50.1 1.6
5 mga-53543 typical noise parameters t c = 25c, v d = 5.0v, i d = 54 ma, z o = 50 , (in icm test fxture) freq f min opt opt r n /z o g a (ghz) (db) mag ang (db) 0.5 1.07 0.108 156.5 0.1 19.13 0.8 1.11 0.144 173. 0.09 18.8 0.9 1.1 0.159 175.3 0.09 18.08 1.0 1.14 0.171 173.9 0.09 17.89 1.1 1.14 0.13 166.3 0.08 17.71 1.5 1. 0.38 -179 0.08 16.99 1.8 1.3 0.3 -175. 0.09 16.45 1.9 1.31 0.9 -17 0.09 16.7 .0 1.34 0.37 -169.3 0.09 16.07 .1 1.36 0.43 -167.3 0.09 15.88 . 1.35 0.54 -165 0.09 15.69 .3 1.4 0.55 -163. 0.09 15.49 .4 1.44 0.64 -159.9 0.09 15.9 .5 1.49 0.7 -158 0.1 15.09 3.0 1.59 0.98 -14.3 0.1 14.1 3.5 1.64 0.369 -131. 0.13 13.14 3.8 1.71 0.4 -13.8 0.16 1.56 3.9 1.74 0.41 -13 0.17 1.39 4.0 1.76 0.417 -10. 0.18 1.19 4.5 1.96 0.469 -108 0.6 11.3 5.0 .11 0.51 -99.4 0.35 10.34 5.5 .38 0.555 -90.1 0.49 9.4 5.7 .49 0.563 -87.3 0.56 9.04 5.8 .51 0.568 -84.3 0.6 8.84 5.9 .54 0.583 -8.7 0.64 8.7 6.0 .61 0.579 -81.7 0.66 8.5 6.5 .81 0.613 -7.1 0.9 7.66 7.0 3.14 0.63 -63.1 1.17 6.71 7.5 3.48 0.65 -5 1.56 5.78 8.0 3.81 0.673 -4 .05 4.9 8.5 4.07 0.694 -3.5 .56 4.11 9.0 4.16 0.741 -.7 3.1 3.47 9.5 4.18 0.778 -16.7 3.89 3. 10.0 4.6 0.771 -8.9 4.48 .41 mga-53543 typical linearity parameters t c = 25c, v d = 5v, z o = 50 freq source [1] source [1] load [1] load [1] oip3 mag () mag () (dbm) 500 mhz 0.31 -10 0.5 -13 40 900 mhz 0.15 -90 0.05 -165 40 1.9 ghz 0.38 156 0.05 45 39 .4 ghz 0.49 177 0.17 141 36 note: 1. input and output tuners tuned for maximum oip3 while keeping vswr better than :1
6 figure 1. matching for linearity at 1900 mhz. l s rfc +5v l1 c1 r1 rf in 1 3 4 2 c3 c4 53 c2 rf ou t supply voltage (v) figure 3. gain, noise figure and p1db vs. supply voltage at 1900 mhz. nf, gain, and p 1db (db) 1 20 15 10 5 0 5 2 4 3 nf gain p 1db mga-53543 applications information description the mga-53543 is a highly linear enhancement mode phemt (pseudomorphic high electron mobility transistor) amplifer with a frequency range extending from 450 mhz to 6 ghz. this range makes the mga-53543 ideal for both cellular and pcs basestation applications. with high ip3 and low noise fgure, the mga-53543 may be utilized as a driver amplifer in a transmit chain or as a frst or second stage lna in a receive chain or any other application requiring high linearity. the mga-53543 operates from a +5 volt power supply and draws a nominal current of 53.8 ma. the rfic is contained in a miniature sot-343 (sc-70 4-lead) package to minimize printed circuit board space. this package also ofers good thermal dissipation and rf characteristics. application guidelines for most applications, all that is required to operate the mga is to apply a dc bias of +5 volts and match the rf input and output. rf input the frst step to achieve maximum linearity is to match the input of mga-53543 to one of the linearity values listed on the data sheet. for example, at 1900 mhz the mga-53543 needs to see a complex impedance of 0.38 156 looking towards the source and an output imped - ance of 0.05 45 looking towards the load. this may be accomplished by a conjugate match from the system input impedance (typically 50?) to s * . figure 10 shows the location of these input and output gammas ( s and l ) required for a high linearity. figure 10. matching for linearity at 1900 mhz. rf output few matching elements are required on the output of the mga-53543 to achieve good linearity because the output gamma ( l ) is close to 50?. dc bias to bias the mga-53543, a +5 volt supply is connected to the output pin through an inductor, rfc, which isolates the inband signal from the dc supply as shown in figure . capacitor c3 serves as an rf bypass for inband signals while c4 helps eliminate out of band low frequency sig - nals. an optional resistor r1 may be added to de-q any resonance created between c3 and c4. typically values range from . ? to 10?. a dc blocking capacitor, c , is used at the output of the mmic to isolate the supply volt - age from succeeding circuits. figure 11. schematic diagram with bias connections. operating at other voltages operating this rfic at voltages less than 5v will afect nf, gain, p1db and ip3. figure 1 below demonstrates the afects of changing supply voltage at 1900 mhz. figure 12. gain, nf and p1db vs. supply voltage at 1900 mhz. the afects of supply voltage on oip3 and current at 1900 mhz are shown in table 1. the mga - 53543 is internally biased for optimal performance at a quiescent current of 53.8 ma.
7 50 ? s22* l s22 l * 50 ? input match output match 53 s11 s * s11* gain ip3 nf s opt * opt 1.30 0.051 0.60 0.024 0.9 0.035 dimensions in mm inches 1.15 0.045 2.00 0.079 1.00 0.039 53 rf output rf input figure 15. microstripline layout. table 1. oip3 vs. supply power. voltage oip3 id (v) (dbm) (ma) 1v 0 4 v 17 16 3v 8 4 4v 35 41 5v 39 51 matching the most important criterion when designing with the mga - 53543 is choosing the input and output-matching network. the mga-53543 is designed to give excellent ip3 performance, however to achieve this requires both the input and output matching network to present specifc impedances ( s and l ) to the device. it is also possible to match this part for best nf or best gain. however, this will impact the ip3 performance. to achieve best noise fgure, the input match will need to be modifed to pres - ent gamma opt to the device. to achieve the best gain will require both the input and output to be conjugately matched (which will also result in the best return loss). where needed, the match presented to the input and the output of the device can be modifed to compromise between ip3, nf and gain performance. the mga-53543 has isolation large enough to allows input and output refection coefcients to be replaced by s11 and s . in general matching for minimum noise fgure does not necessarily guarantee good ip3 performance nor does it guarantee good gain. this is due to the fact that the impedance parameters shown below in table are not guaranteed to lie near each other on a smith chart. so, ideally if all input matching parameters lied near each other or at the same point, and all output parameters also lied near each other or at the same point, the amplifer would have minimum noise figure, maximum ip3 and maximum gain all with a single match. typically this is not the case and some parameter must be sacrifced to improve another. table briefy lists the input and output parameters required for each type of match while figure 13 depicts how each is defned. figure 13. defnition of matching parameters. figure 14. recommended pcb pad layout for avagos sc70 4l/sot-343 products. this layout provides ample allowance for package place - ment by automated assembly equipment without add - ing parasitics that could impair the high frequency rf performance of the mga-53543. the layout is shown with a footprint of a sot-343 package superimposed on the pcb pads for reference. a microstrip layout with sufcient ground vias as shown in figure 6 is recommended for the mga - 53543 in transitioning from a package pad layout as in figure 14. table 2. required matching for nf, ip3, input & output return loss and gain. match input output for tuning tuning ip3 s l nf opt none rl in s11* none rl out none s* gain s11* s* pcb layout a recommended pcb pad layout for the miniature sot- 343 (sc - 70) package used by the mga-53543 is shown in figure 14.
8 rf grounding adequate grounding of pins 1 and 4 of the rfic are impor - tant to maintain device stability and rf performance. each of the ground pins should be connected to the ground plane on the backside of the pcb by means of plated through holes (vias). the ground vias should be placed as close to the package terminals as practical to reduce induc - tance in ground path. it is good practice to use multiple vias to further minimize ground path inductance. pcb materials fr-4 or g-10 type material is a good choice for most low cost wireless applications using single or multi-layer printed circuit boards. typical single-layer board thickness is 0.0 0 to 0.031 inches. circuit boards thicker than 0.031 inches are not recommended due to excessive inductance in the ground vias. for noise fgure critical or higher frequency applications, the additional cost of ptfe/glass dielectric materials may be warranted to minimize transmission line loss at the amplifers input. application example the demonstration circuit board for the mga-53543 is shown in figure 16. this simple two-layer board contains microstripline on the topside and a solid metal ground plane on the backside with all rf traces having charac - teristic impedance of 50?. multiple 0.0 " vias are used to bring the ground to the topside of the board and help reduce ground inductance. the pcb is fabricated on 0.031" thick getek? gr 00d dielectric material with dielectric constant of 4. . figure 8. noise figure performance. nf = 1.5 db nf = 1.6 db nf = 1.7 db opt ? optimum nf match s ? optimum linearity match figure 9. input and output gain circles. ga = 15.9 db ga = 16.1 db ga = 16.2 db ga = 16.1 db ga = 16.2 db s11 s22 l s figure 18. input and output gain circles. figure 17. noise fgure performance. because gain depends both on the input and output match, the maximum gain is taken from two sets of circles. one is centered around s11 and the other is centered on s . thus the maximum attainable gain is the lesser of two circles which completely enclose s or l . for example, in figure 18 the 16.1 db input gain circle completely encloses s , but the smallest circle that encloses l is 15.9 db. thus the maximum gain is the weakest link or 15.9 db. figure 16. mga-53453 pcb layout. 1900 mhz hla design the following describes a typical application for the mga- 53543 as used in a pcs 1900 mhz band radio receiver optimized for maximum linearity. steps include matching the input and output as well as providing a dc bias while maintaining acceptable stability, gain and noise fgure. as described earlier, a pure linearity match entails match - ing only to s and l , thus sacrifcing some nf and gain. this tradeof is explained below and quantifed in figures 8 and 9. using the device s-parameters at 1900 mhz, the minimum noise fgure possible, whilst matching the input to s , is shown to be 1.7 db. in out vd se 12/01 mga - 5x
9 to accomplish the above performance, a high pass con - fguration consisting of a 3.3 nh inductor and a . pf capacitor is used for the input match. unlike a low pass confguration, a high pass confguration provides not only the impedance transfer required, but also provides excellent stability for the demo board by diminishing low frequency gain. no matching is required for the output, but a good rule of thumb to use when biasing is to limit series reactance to less than 5? and keep shunt reactance above 500?. therefore choosing an rfc of 47 nh, which has a reac - tance of 561? at 1.9 ghz, helps isolate the dc supply from inband signals. if any high frequency signal is created or enters the dc supply, a 150 pf capacitor is ready to short it to ground. an 8. pf capacitor serves primarily as a dc block, but also helps the output match. the completed 1900 mhz amplifer schematic is shown in figure 19. 2.2 ? 0.1 f +5v 47 nh 3.3 nh 3 4 1 2 8.2 pf 150 pf 2.2 pf rf in rf out 53 figure 19. schematic for a 1900 mhz stable circuit. included with the schematic is a complete rf layout (fig - ure 4) which includes placement of all components and sma connectors. a list of part numbers and manufacturer used is given below in table 3. table 3. component parts list for the mga - 53543 hla at 1900 mhz. 3.3 nh toko ll1608-fs3n3s 47 nh toko ll1005-fh47n . rhom mcr01jr . pf phycomp 040 cg9c9b00 8. pf phycomp 040 cg89d9b00 150 pf phycomp 040 cg151j9b00 0.1 f phycomp 0603 f104m8b0 performance of mga-53543 at 1900 mhz with a device voltage of +5v, demonstration board mga- 5x delivers a measured noise fgure of 1.78 db and an average gain of 14.5 db as shown in figure 0. gain here is slightly lower than data sheet due to the losses acquired in creating a stable broadband match. input and output vswr are both better than :1 at 1900 mhz, with input return loss being 10 db and output return loss at 13 db. frequency (ghz) figure 11. gain and noise figure vs frequency. gain and nf (db) 1.6 20 15 10 5 0 2.6 1.8 2.2 2.4 2 gain nf frequency (ghz) figure 12. input and output return loss vs frequency. return loss (db) 1.6 0 -5 -10 -15 -20 -25 2.6 1.8 2.2 2.4 2 s11 s22 frequency (mhz) figure 13. oip3 vs frequency. oip3 (dbm) 1840 45 40 35 30 25 2000 1880 1920 1960 rx tx figure 22. oip3 vs. frequency. due to component parasitics and part variations, actual performance may not be identical to this example. figure 21. input and output return loss vs frequency. more signifcant is the linearity delivered by mga-53543 at 1900 mhz. figure plots oip3 over a frequency range from 1850 mhz to1950 mhz. this device produces iip3 of 4 dbm, oip3 of 38 dbm and p1db of 17.8 dbm at 1900 mhz. figure 20. gain and noise figure vs frequency.
10 900 mhz hla design optimizing the mga-53543 for maximum linearity at the cellular band follows very similar to that of 1900 mhz, except that the input and output tuning conditions will change according to the linearity table on the data sheet. figure 14 below shows the schematic diagram for a com - plete 900 mhz circuit using s of 0.15 -90 and l of 0.05 -165. table 4 shows the component parts list used. an optional . ? resistor at the input helps resistively load the amplifer and improve stability but slightly degrade noise fgure. figure 24. rf layout for 1900 mhz hla . 2.2 ? 2.2 ? +5v 15 nh 22 nh 3 4 1 2 4.7 pf 1000 pf 5.6 pf rf in rf out 53 figure 23 . schematic diagram for 900 mhz hla. table 4. component parts list for the mga - 53543 hla at 900 mhz. nh toko ll1608-fs n 15 nh toko ll1005-fs15n . rhom mcr01jr 4.7 pf phycomp 040 cg479c9b00 5.6 pf phycomp 040 cg569d9b00 1000 pf phycomp 040 r10k9b00 frequency (mhz) figure 16. gain and noise figure vs frequency. gain and nf (db) 400 20 15 10 5 0 1400 600 1000 1200 800 gain nf frequency (mhz) figure 17. input and output return loss vs frequency. return loss (db) 400 0 -5 -10 -15 -20 1400 600 1000 1200 800 s11 s22 performance of mga-53543 at 900 mhz at 900 mhz mga-53543 delivers oip3 of 40 dbm along with a noise fgure of 1.43 db. gain is measured to be 17.1 db and input return loss is 13.7 db and output re - turn loss is 13.3 db as shown in figures 16 and 17. p1db is 18.8 dbm. figure 25. gain and noise figure vs frequency. figure 26. input and output return loss vs frequency. in c1 l1 r1 j1 out l2 c2 j2 c3 r2 vd se 02/01 mga - 5x 53
11 2.2 ? +5v 15 nh 12 nh 3 4 1 2 4.7 pf 1000 pf 4.7 pf rf in rf out 53 frequency (mhz) figure 19. gain, noise figure and output power at 900 mhz. gain and nf (db) 400 20 15 10 5 0 1400 600 1000 1200 800 gain nf frequency (mhz) figure 20. input and output return loss at 900 mhz. return loss (db) 400 0 -5 -10 -15 -20 -25 -30 1400 600 1000 1200 800 s11 s22 figure 27. schematic for 900 mhz lna design. table 5. component parts list for the mga - 53543 hla at 900 mhz. 1 nh toko ll1608-fs1 nj 15 nh toko ll1005-fs15n 4.7 pf phycomp 040 cg479c9b00 . rhom mcr01jr 1000 pf phycomp 040 r10k9b00 performance of mga-53543 at 900 mhz biased with a +5 volt supply mga-53543 delivers a noise figure of 1.33 db at 900 mhz. this number is higher than nf min only because of loss from lumped element com - ponents with parasitic losses. a microstip or distributed element match may improve noise fgure by . db. gain is measured to be 17.4 db as shown in figure 8. input and output vswr are both better than :1, with input return loss of 5 db and output return loss at 17.5 db shown in figure 9. figure 28. gain, noise figure and output power at 900 mhz. figure 29. input and output return loss at 900 mhz. input iip3 is measured to be 18.6 dbm and p1db is 19.0 db at 900 mhz. 900 mhz lna design to demonstrate the versatility of the mga-53543, the following example describes a cellular band low noise amplifer (lna) design. the methodology for a 900 mhz lna design difers from the previous examples in that only the input match afects noise fgure. thus, optimiz - ing for minimum noise fgure entails matching only the input to opt instead of s , and the output can either be matched to s for better gain or l for better linearity. figure 7 shows the complete schematic for a 900 mhz low noise amplifer design and table 5 describes the re - quired components.
1 2.2 ? +5v 47 nh 3.9 nh 3 4 1 2 8.2 pf 150 pf 2.2 pf rf in rf out 53 1900 mhz lna design the fnal example presented in this application note is a pcs band low noise amplifer circuit. as in the 900 mhz lna example, the input is matched to opt which at 1900 mhz is given as . 9 -17 and the output is matched for maximum linearity i.e. l . biasing the dc supply is done very similar to the 1900 mhz hla. in fact, the only major diference between the pcs hla presented earlier and this pcs lna schematic is a 3.9nh inductor on the input. the complete schematic is shown below. figure 30. schematic for 1900 mhz lna design. table 6 shows the complete parts list used for the 1900 mhz low noise amplifer. table 6. component parts list for the mga - 53453 lna amplifer at 1900 mhz. 3.9 nh toko ll1608-fs3n9s 47 nh toko ll1005-fh47n . rhom mcr01jr . pf phycomp 040 cg9c9b00 8. pf phycomp 040 cg89d9b00 150 pf phycomp 040 cg151j9b00 frequency (ghz) figure 22. gain, noise figure vs frequency for 1900 mhz lna. gain and nf (db) 1.6 20 15 10 5 0 2.6 1.8 2.2 2.4 2.0 gain nf frequency (ghz) figure 23. input and output return loss for 1900 mhz lna. return loss (db) 1.6 0 -5 -10 -15 -20 -25 2.6 1.8 2.2 2.4 2.0 s11 s22 figure 32. input and output return loss for 1900 mhz lna. figure 31. gain, noise figure vs. frequency for 1900 mhz lna. performance of mga-53543 at 1900 mhz the typical noise fgure for the 1900 mhz lna is measured to be 1.6 db with oip3 at a nominal 37 dbm. figure 31 shows a measured gain of 14.8 db and figure 3 shows the input and output return loss to be 16.4 db and 11.3 db respectively. p1db is 18 dbm.
13 part number ordering information no. of part number devices container mga-53543-tr1g 3000 7" reel mga-53543-tr g 10000 13" reel MGA-53543-BLKG 100 antistatic bag device model refer to avagos web site www.avagotech.com/view/rf summary in summary, the mga-53543 offers very high ip3 as designed, but is versatile enough to give good nf per - formance wherever needed. below is a summary of the preceding four examples. table 7. 1900 mhz and 900 mhz hla and 1900 mhz and 900 mhz lna sum - mary. 1900 mhz 900 mhz nf = 1.78 db nf = 1.4 db hla oip3 = 38 dbm oip3 = 40 dbm ga = 14.5 db ga = 17.1 db p1db = 17.8 dbm p1db = 18.8 dbm nf = 1.6 db nf = 1.33 db lna oip3 = 37 dbm oip3 = 36 dbm ga = 14.8 db ga = 17.4 db p1db = 18.0 dbm p1db = 19.0 dbm package dimensions outline 43 (sot-343/sc70 4 lead) he d a2 a1 b b1 e 1.30 (.051) bsc 1.15 (.045) bsc c l a dimensions (mm) min. 1.15 1.85 1.80 0.80 0.80 0.00 0.25 0.55 0.10 0.10 max. 1.35 2.25 2.40 1.10 1.00 0.10 0.40 0.70 0.20 0.46 symbol e d he a a2 a1 b b1 c l notes: 1. all dimensions are in mm. 2. dimensions are inclusive of plating. 3. dimensions are exclusive of mold flash & metal burr. 4. all specifications comply to eiaj sc70. 5. die is facing up for mold and facing down for trim/form, ie: reverse trim/form. 6. package surface to be mirror finish.
tape dimensions for outline 4t p p 0 p 2 f w c d 1 d e a 0 10 max. t 1 (carrier tape thickness) t t (cover tape thickness) 10 max. b 0 k 0 description symbol size (mm) size (inches) length width depth pitch bottom hole diameter a 0 b 0 k 0 p d 1 2.40 0.10 2.40 0.10 1.20 0.10 4.00 0.10 1.00 + 0.25 0.094 0.004 0.094 0.004 0.047 0.004 0.157 0.004 0.039 + 0.010 cavity diameter pitch position d p 0 e 1.55 0.10 4.00 0.10 1.75 0.10 0.061 + 0.002 0.157 0.004 0.069 0.004 perforation width thickness w t 1 8.00 + 0.30 - 0.10 0.254 0.02 0.315 + 0.012 0.0100 0.0008 carrier tape cavity to perforation (width direction) cavity to perforation (length direction) f p 2 3.50 0.05 2.00 0.05 0.138 0.002 0.079 0.002 distance width tape thickness c t t 5.40 0.10 0.062 0.001 0.205 + 0.004 0.0025 0.0004 cover tape for product information and a complete list of distributors, please go to our web site: www.avagotech.com avago, avago technologies, and the a logo are trademarks of avago technologies in the united states and other countries. data subject to change. copyright ? 2005-2008 avago technologies. all rights reserved. obsoletes 5989-3741en av02-0455en - august 27, 2008 device orientation u s e r f e e d d i r e c t i o n c o v e r t a p e c a r r i e r t a p e r e e l e n d v i e w 8 m m 4 m m t o p v i e w ( p a c k a g e m a r k i n g e x a m p l e o r i e n t a t i o n s h o w n . ) 5 3 x 5 3 x 5 3 x 5 3 x

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