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EL4094C august 1996, rev d EL4094C video gain control/fader note: all information contained in this data sheet has been carefully checked and is believed to be accurate as of the date of publication; however, this data sheet cannot be a ``controlled document''. current revisions, if any, to these specifications are maintained at the factory and are available upon your request. we recommend checking the revision level before finalization of your design documentation. ? 1993 elantec, inc. features # complete video fader # 0.02%/0.04 differential gain/ phase @ 100% gain # output amplifier included # calibrated linear gain control # g 5v to g 15v operation # 60 mhz bandwidth # low thermal errors applications # video faders/wipers # gain control # video text insertion # level adjust # modulation ordering information part no. temp. range package outline y EL4094Cn b 40 cto a 85 c 8-pin p-dip mdp0031 EL4094Cs b 40 cto a 85 c 8-pin so mdp0027 general description the EL4094C is a complete two-input fader. it combines two inputs according to the equation: v out e v ina (0.5v a vg) a v inb (0.5v b vg), where v gain is the difference between v gain and v gain pin voltages and ranges from b 0.5v to a 0.5v. it has a wide 60 mhz bandwidth at b 3 db, and is designed for excellent video distortion performance. the EL4094C is the same circuit as the el4095, but with feedback resistors included on-chip to imple- ment unity-gain connection. an output buffer is included in both circuits. the gain-control input is also very fast, with a 20 mhz small- signal bandwidth and 70 ns recovery time from overdrive. the EL4094C is compatible with power supplies from g 5v to g 15v, and is available in both the 8-pin plastic dip and so-8. connection diagram 4094 1 manufactured under u.s. patent no. 5,321,371, 5,374,898
EL4094C video gain control/fader absolute maximum ratings (t a e 25 c) v s a voltage between v s a and gnd a 18v v s voltage between v s a and v s b a 33v v ina , input voltage (v s b ) b 0.3v v inb to (v s a ) a 0.3v v gain input voltage v gain g 5v v gain input voltage v s b to v s a i out output current g 35 ma internal power dissipation see curves t a operating ambient temp. range b 40 cto a 85 c t j operating junction temperature 150 c t st storage temperature range b 65 cto a 150 c important note: all parameters having min/max specifications are guaranteed. the test level column indicates the specific device testing actually performed during production and quality inspection. elantec performs most electrical tests using modern high-speed automatic test equipment, specifically the ltx77 series system. unless otherwise noted, all tests are pulsed tests, therefore t j e t c e t a . test level test procedure i 100% production tested and qa sample tested per qa test plan qcx0002. ii 100% production tested at t a e 25 c and qa sample tested at t a e 25 c, t max and t min per qa test plan qcx0002. iii qa sample tested per qa test plan qcx0002. iv parameter is guaranteed (but not tested) by design and characterization data. v parameter is typical value at t a e 25 c for information purposes only. open loop dc electrical characteristics v s e g 5v, t a e 25 c, v gain ea 0.6v to measure channel a, v gain eb 0.6v to measure channel b, v gain e 0v, unless otherwise specified parameter description limits level test units min typ max v os input offset voltage 4 30 i mv i b a v in input bias current 2 10 i m a psrr power supply rejection ratio 60 80 i db eg gain error, 100% setting b 0.5 b 0.8 i % v in v in range (v b ) a 2.5 (v a ) b 2.5 i v v o output voltage swing (v b ) a 2.5 (v a ) b 2.5 i v i sc output short-circuit current 50 95 150 i ma v gain , 100% minimum voltage at v gain for 100% gain 0.45 0.5 0.55 i v v gain , 0% maximum voltage at v gain for 0% gain b 0.55 b 0.5 b 0.45 i v nl, gain gain control non-linearity, v in e g 0.5v 1.5 4 i % nl, a v e 1 signal non-linearity, v in e 0to g 1v, v gain e 0.55v 0.01 v % a v e 0.5 signal non-linearity, v in e 0to g 1v, v gain e 0v 0.05 v % a v e 0.25 signal non-linearity, v in e 0to g 1v, v gain eb 0.25v 0.2 0.5 i % r gain resistance between v gain and v gain 4.6 5.5 6.6 i k x i s supply current 12 14.5 19 i ma f t off-channel feedthrough b 75 b 50 i db 2 td is 0.6in td is 3.3in
EL4094C video gain control/fader closed loop ac electrical characteristics v s e g 15v, c l e 15 pf, t a e 25 c, a v e 100% unless otherwise noted parameter description limits level test units min typ max sr slew rate; v out from b 3v to a 3v measured at b 2v and a 2v 370 500 v v/ m s bw bandwidth, b 3 db 45 60 iii mhz b 1 db 35 v mhz b 0.1 db 6 v mhz dg differential gain, ac amplitude of 286 mv p-p at 3.58 mhz on dc offset of b 0.7, 0, and a 0.7v a v e 100% 0.02 v % a v e 50% 0.20 v % a v e 25% 0.40 v % d i differential phase, ac ampitude of 286 mv p-p at 3.58 mhz on dc offset of b 0.7, 0, and a 0.7v a v e 100% 0.04 v ( ) a v e 50% 0.20 v ( ) a v e 25% 0.20 v ( ) bw, gain b 3 db gain control bandwidth, v gain amplitude 0.5 v p-p 20 v mhz t rec , gain gain control recovery from overload; v gain from b 0.6v to 0v 70 v ns typical performance curves small-signal step response for gain e 100%, 50%, 25%, and 0%. v s g 5v 4094 2 large-signal step response for gain e 100%, 50%, 25%, and 0%. v s g 12v 4094 3 3 td is 2.6in
EL4094C video gain control/fader typical performance curves e contd. capacitive loading frequency response vs resistive loading frequency response vs frequency response vs gain over frequency off-channel isolation bandwidth with supply voltage change in slewrate and output noise over frequency 4094 4 4
EL4094C video gain control/fader typical performance curves e contd. bandwidth over temperature supply current, slewrate and change in 100% gain error, gain e 100%, 75%, 50% and 25% nonlinearity vs v in for 75%, 50% and 25%. f e 3.58 mhz v offset for gain e 100%, differential gain error vs 75%, 50% and 25%. f e 3.58 mhz v offset for gain e 100%, differential phase error vs 75%, 50% and 25%. f e 3.58 mhz v offset for gain e 100%, differential gain error vs 75%, 50% and 25%. f e 3.58 mhz v offset for gain e 100%, differential phase error vs 4094 5 5
EL4094C video gain control/fader typical performance curves e contd. phase error vs gain differential gain and phase error vs gain differential gain and 4094 6 gain vs v g .1v dc at v ina 4094 7 cross-fade balance. v ina e v inb e 0v 4094 8 gain control response to a non-overloading step, constant sinewave at v ina 4094 9 v gain overload recovery response 4094 10 6
EL4094C video gain control/fader typical performance curves e contd. gain control gain vs frequency gain control vs /v g offset change in v(100%) and v(0%) of control vs supply voltage change in v(100%) and v(0%) of gain control vs die temperature change in v(100%) and v(0%) of gain supply current vs supply voltage ambient temperature maximum dissipation vs 4094 11 7
EL4094C video gain control/fader applications information the el4094 is a self-contained and calibrated fader subsystem. when a given channel has 100% gain the circuit behaves as a current-feed- back amplifier in unity-gain connection. as such, video and transfer distortions are very low. as the gain of the input is reduced, a 2-quadrant multiplier is gradually introduced into the signal path and distortions increase with reducing gain. the input impedance also changes with gain set- ting, from about 1 m x at 100% gain down to 16 k x at zero gain. to maximize gain accuracy and linearity, the inputs should be driven from source impedances of 500 x or less. linearity the el4094 is designed to work linearly with g 2v inputs, but lowest distortion occurs at g 1v levels and below. errors are closer to those of a good current-feedback amplifier above 90% gain. low-frequency linearity is 0.1% or better for gains 25% to 100% and inputs up to 1v. ntsc differential gain and phase errors are better than 0.3% and 0.3 for the 25% to 100% gain range. these distortions are not strongly affected by supply voltage nor output loading, at least down to 150 x . for settling to 0.1%, however, it is best to not load the output heavily and to run the el4094 on the lowest practical supply voltages, so that thermal effects are minimized. gain control inputs the gain control inputs are differential and may be biased at any voltage as long as /v gain is less than 2.5v below v a and 3v above v b . the dif- ferential input impedance is 5.5 k x , and the com- mon-mode impedance is more than 500 k x . with zero differential voltage on the gain inputs, both signal inputs have a 50% gain factor. nominal calibration sets the 100% gain of v ina input at a 0.5v of gain control voltage, and 0% at b 0.5v of gain control. v inb 's gain is complementary to that of v ina ; a 0.5v of gain control sets 0% gain at v inb and b 0.5v gain control sets 100% v inb gain. the gain control does not have a complete- ly abrupt transition at the 0% and 100% points. there is about 10 mv of ``soft'' transfer at the gain endpoints. to obtain the most accurate 100% gain factor or best attenuation at 0% gain, it is necessary to overdrive the gain control input by 30 mv or more. this would set the gain con- trol voltage range as b 0.565v to a 0.565v, or 30 mv beyond the maximum guaranteed 0% to 100% range. in fact, the gain control inputs are very complex. here is a representation of the ter- minals: 4094 12 representation of gain control inputs v g and /v g for gain control inputs between g 0.5v ( g 90 m a), the diode bridge is a low impedance and all of the current into vg flows back out through/v g . when gain control inputs exceed this amount, the bridge becomes a high imped- ance as some of the diodes shut off, and the v g impedance rises sharply from the nominal 5.5k x to about 500k x . this is the condition of gain control overdrive. the actual circuit produces a much sharper overdrive characteristic than does the simple diode bridge of this representation. the gain input has a 20 mhz b 3 db bandwidth and 17 ns risetime for inputs to g 0.45v. when the gain control voltage exceeds the 0% or 100% values, a 70 ns overdrive recovery transient will occur when it is brought back to linear range. if quicker gain overdrive response is required, the force control inputs of the el4095 can be used. output loading the el4094 does not work well with heavy ca- pacitive loads. like all amplifier outputs, the out- put impedance becomes inductive over frequency resonating with a capacitive load. the effective output inductance of the el4094 is about 350 nh. more than 50 pf will cause excessive fre- quency response peaking and transient ringing. the problem can be solved by inserting a low- value resistor in series with the load, 22 x or more. if a series resistance cannot be used, then adding a 300 x or less load resistor to ground or a ``snubber'' network may help. a snubber is a re- 8
EL4094C video gain control/fader applications information e contd. sistor in series with a capacitor, 150 x and 100 pf being typical values. the advantage of a snubber is that it does not draw dc load current. unterminated coaxial line loads can also cause resonances, and they should be terminated either at the far end or a series back-match resistor in- stalled between the el4094 and the cable. the output stage can deliver up to 140 ma into a short-circuit load, but it is only rated for a con- tinuous 35 ma. more continuous current can cause reliability problems with the on-chip metal interconnect. video levels and loads cause no problems at all. noise the el4094 has a very simple noise characteris- tic: the output noise is constant (40 nv/ s hz wideband) for all gain settings. the input-re- ferred noise is then the output noise divided by the gain. for instance, at a gain of 50% the input noise is 40 nv/ s hz/0.5, or 80 nv/ s hz. bypassing the el4094 is fairly tolerant of power-supply bypassing, but best multiplier performance is ob- tained with closely connected 0.1 m f ceramic ca- pacitors. the leaded chip capacitors are good, but neither additional tantalums nor chip compo- nents are necessary. the signal inputs can oscil- late locally when connected to long lines or un- terminated cables. power dissipation peak die temperature must not exceed 150 c. at this temperature, the epoxy begins to soften and becomes unstable, chemically and mechanically. this allows 75 c internal temperature rise for a 75 c ambient. the el4094 in the 8-pin pdip package has a thermal resistance of 87 /w, and can thus dissipate 862 mw at a 75 c ambient temperature. the device draws 17 ma maximum supply current, only 510 mw at g 15v supplies, and the circuit has no dissipation problems in this package. the so-8 surface-mount package has a 153 /w thermal resistance with the el4094, and only 490 mw can be dissipated at 75 c ambient tem- perature. the el4094 thus cannot be operated with g 15v supplies at 75 c in the surface-mount package; the supplies should be reduced to g 5v to g 12v levels, especially if extra dissipation oc- curs when driving a load. the el4094 as a level adjust a common use for gain controls is as an input signal levellerea circuit that scales too-large or too-small signals to a standard amplitude. a typi- cal situation would be to scale a variable video input by a 6dbto b 6 db to obtain a standard amplitude. the el4094 cannot provide more than 0 db gain, but it can span the range of 0 db to b 12 db with another amplifier gaining the output up by 6 db. the simplest way to obtain the range is to simply ground the b input and vary the gain of the signal applied to the a input. the disadvantage of this approach is that lineari- ty degrades at low gains. by connecting the sig- nal to the a input of the el4094 and the signal attenuated by 12 db to the b input, the gain con- trol offers the highest linearity possible at 0 db and b 12 db extremes, and good performance be- tween. the circuit is shown on the following page. the el4095 can be used to provide the required gains without the extra amplifier. in practice, the gain control is adjusted to set a standard video level regardless of the input level. the el4583 sync-separator has a recovered amplitude output that can be used to servo the gain control volt- age. here is the curve of differential gain and phase distortion for varying inputs, with the out- put set to standard video level: 4094 14 differential gain and phase of linearized level control 9
EL4094C video gain control/fader applications information e contd. the differential gain error is kept to 0.3% and the differential phase to 0.15 or better over the entire input range. the el4094 as an adjustable filter equalizers are used to adjust the delay or fre- quency response of systems. a typical use is to compensate for the high-frequency loss of a cable system ahead of the cable so as to create a flat response at the far end. a generalized scheme with the el4094 is shown below. for an adjustable preemphasis filter, for instance, filter a might be an all-pass filter to compensate for the delay of filter b, a peaking filter. fading the gain from a to b provides a variable amount of peaking, but constant delay. the el4094 as a phase modulator to make a phase modulator, filter a might be a leading-phase network, and filte r b a lagging net- work. the wide bandwidth of the gain-control in- put allows wideband phase modulation of the carrier applied to the main input. of course, the carrier and gain inputs must not be digital but be reasonably clean sinewaves for the modulation to be accurate. 4094 13 a 6dbto b 6 db linearized level control 4094 15 general adjustable equalizer 10
EL4094C video gain control/fader EL4094C macromodel this macromodel is offered to allow simulation of general el4094 behavior. we have included these characteristics: small-signal frequency response output loading effects input impedance off-channel feedthrough output impedance over frequency signal path dc distortions v gain i-v characteristics v gain overdrive recovery delay 100% gain error these will give a good range of results for various operating conditions, but the macromodel does not behave identically as the circuit in these ar- eas: temperature effects signal overload effects signal and /v g operating range current-limit video and high-frequency distortions supply voltage effects slewrate limitations noise power supply interactions the macromodel's netlist is based on the pspice simulator (copywritten by the microsim compa- ny). other simulators may not support the poly function, which is used to implement mul- tiplication as well as square-low nonlinearities. ****** ****** * v inb * l v out * ll /v g * lll v g * llll v ina * lllll .subckt el4094subckt (1 4 6 7 8) *** r ol 810 0 290k ccomp 810 0 3.5p g1 10 0 810 0 b 10 r out 10 0 0.1 l out 10 4 350.200n rl out 10480 r1 10 910 10 c1 910 911 300p r2 911 0 90 *** *** input channel a *** r ina 22 910 16k ra 11 0 1k cfeedthrougha 23 8 130p rfeedthrougha 8 22 1.0 ela 23 22 1 0 1.0 rspice3 23 22 1e12 g1a 11 0 poly(1) (22, 910) 0.0 0.001 b 3e b 6 g2a 810 0 poly(2) (11,0) (13, 0) 0.0 0.0 0.0 0.0 0.001 *** *** input channel b *** r inb 25 910 16k rb 20 0 1k cfeedthroughb 24 1 130p rfeedthroughb 1 25 1.0 e1b 24 25 8 0 1.0 rspice4 24 25 1e12 g1b 20 0 poly(1) (25, 910) 0.0 0.001 b 3e b 6 g2b 810 0 poly(2) (20,0) (19, 0) 0.0 0.0 0.0 0.0 0.001 *** *** gain control *** rspice1 13 0 1e12 rspice2 18 0 1e12 r10 14 0 1e7 c10 14 0 8e b 16 d1 14 15 dclamp d2 16 14 dclamp .model dclamp d (tt e 200n) v1 15 0 4999.3 v2 0 16 4999.3 v3 13 17 0.5 v4 19 18 0.5 g1014076 b 0.001 g1176140 b 2e b 8 e101701401e b 4 e11180140 b 1e b 4 *** .ends ****** 11 tab wide td is 1.3in tab wide td is 6.8in
EL4094C august 1996, rev d EL4094C video gain control/fader EL4094C macromodel e contd. 4094 16 el4094 macromodel schematic general disclaimer specifications contained in this data sheet are in effect as of the publication date shown. elantec, inc. reserves the right to make changes in the circuitry or specifications contained herein at any time without notice. elantec, inc. assumes no responsibility for the use of any circuits described herein and makes no representations that they are free from patent infringement. elantec, inc. 1996 tarob court milpitas, ca 95035 telephone: (408) 945-1323 (800) 333-6314 fax: (408) 945-9305 european office: 44-71-482-4596 warning e life support policy elantec, inc. products are not authorized for and should not be used within life support systems without the specific written consent of elantec, inc. life support systems are equipment in- tended to support or sustain life and whose failure to perform when properly used in accordance with instructions provided can be reasonably expected to result in significant personal injury or death. users contemplating application of elantec, inc. products in life support systems are requested to contact elantec, inc. factory headquarters to establish suitable terms & conditions for these applications. elantec, inc.'s warranty is limited to replace- ment of defective components and does not cover injury to per- sons or property or other consequential damages. printed in u.s.a. 12

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