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features description applications tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 synchronous boost converter with down mode high power white led driver 80% efficient synchronous boost converter the tps61058/9 devices are fixed frequency, synchronous boost dc-dc converters with an ? 500-ma led current from 3.3-v input integrated down conversion mode. the devices are (tps61058) optimized for driving high power single cell white ? 800-ma led current from 3.3-v input leds up to 800 ma from a 2.7-v to 5.5-v input. the (tps61059) led current can be programmed to different levels input voltage range: 2.7 v to 5.5 v (e.g. torch, flashlight) by a set of external resistors. fixed frequency 650 khz (typ) operation the boost converter is based on a 650 khz fixed led disconnect during shutdown frequency, pulse-width-modulation (pwm) controller using a synchronous rectifier to obtain maximum open/shorted led protection efficiency. the maximum peak current in the boost over-temperature protection switch is limited to 1000 ma (tps61058) and 1500 low shutdown current: 100 na (typ) ma (tps61059). total solution of less than 80 mm 2 the converter can be disabled to maximize battery small 3mm x 3mm qfn-10 package life. in the shutdown mode, the load is completely disconnected and the current consumption is reduced to less than 1 a. built-in precharge and soft-start circuitry prevents excessive inrush current during torch/camera white led supply for cell start-up. phones, smart-phones and pdas the device is packaged in a 10-pin qfn powerpad? package measuring 3 mm x 3 mm (drc). figure 1. 500 ma flashlight application figure 2. flashlight efficiency vs v in please be aware that an important notice concerning availability, standard warranty, and use in critical applications of texas instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. powerpad is a trademark of texas instruments. production data information is current as of publication date. copyright ? 2005, texas instruments incorporated products conform to specifications per the terms of the texas instruments standard warranty. production processing does not necessarily include testing of all parameters. (3,25 mm x 3,25 mm) www .ti.com 0 10 20 30 40 50 60 70 80 90 100 2.70 3.10 3.50 3.90 4.30 4.70 5.10 5.50 v - input v oltage - v i led power efficiency (p /p ) - % l ed i n i = 500 ma @ v = 3.7 v l ed f c in l1 v in 22 m f 4.7 m h 2.7 v . . 5.5 v gnd tps61058 gnd p v in en vin sw vout fb pgnd c 1 , c2, c3 x3 d1 c 3 r s r2 r1 iok r 3 r 4 flash on (0/ 1.8 v) 22 m f 39 k w 22 k w 56 k w 1.5 w 62 k w 1 nf(cog) r5 5.6 k w
absolute maximum ratings dissipation ratings table tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 these devices have limited built-in esd protection. the leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the mos gates. available options t a current limit package marking package part number (1) (2) 1000 ma bnf tps61058drc -40 c to 85 c 10-pin qfn 1500 ma bng tps61059drc (1) the drc package is available taped and reeled. add r suffix to device type (e.g. tps61058drcr, tps61059drcr) to order quantities of 3000 devices per reel. (2) for the most current package and ordering information, see the package option addendum at the end of this document, or see the ti website at www.ti.com. over operating free-air temperature range (unless otherwise noted) (1) tps61058/9 input voltage range on pvin, vin, en, fb, iok, sw, vout -0.3 v to 7 v power dissipation internally limited operation temperature range, t a -40 c to 85 c maximum operating junction temperature, t j (max) 150 c storage temperature range, t stg -65 c to 150 c (1) stresses beyond those listed under "absolute maximum ratings" may cause permanent damage to the device. these are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under "recommended operating conditions" is not implied. exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. thermal resistance power rating derating factor above package q ja t a 25 c t a = 25 c drc 48.7 c/w 2040 mw 21 mw/ c 2 www .ti.com
electrical characteristics tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 v in = 3.6 v, i led = 500 ma, en = v in , l = 4.7 h, c o = 3x 22 f, t a = ?40 c to 85 c, typical values are at t a = 25 c (unless otherwise noted) dc/dc stage parameter test conditions min typ max unit v in input voltage range v o > 2.0 v @ i led = 50 ma 2.7 5.5 v v out tps61058/9 output voltage range 2.5 5.5 v v ovp output overvoltage protection 5.9 6.1 6.3 v v fb tps61058/9 feedback voltage 490 500 510 mv f oscillator frequency 550 650 750 khz i sw switch current limit (tps61058) v o = 3.3 v 900 1100 1300 ma switch current limit (tps61059) v o = 3.3 v 1200 1500 1800 ma pre-charge current v o = 2.5 v, t a = -10 c to 85 c 84 ma r ds(on) swn switch on resistance v o = 3.3v 260 m w swp switch on resistance v o = 3.3 v 290 m w total accuracy (including line and load regulation) -3% 3% i led = 0 ma, v o = 5.0 v, i q quiescent current 5.5 ma device switching at 650 khz i (sd) shutdown current en = gnd, t a = 25 c 0.1 1 a control stage iok switch on-resistance v o = 5.0 v, i iok = 100 a 0.6 0.8 1 k w iok output low current 100 300 a iok output leakage current v iok = 7 v 0.01 0.1 a v (il) en low-level input voltage 0.4 v v (ih) en high-level input voltage 1.4 v i (i) en input leakage current input tied to gnd 0.01 0.1 a en pull-down resistance 400 k w overtemperature protection 140 c overtemperature hysteresis 20 c 3 www .ti.com
pin assignments tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 terminal functions terminal i/o description name no. en 1 i this is the enable pin of the device. connect this pin to ground forces the device into shutdown mode. pulling this pin above 1.4v enables the device. this pin has an internal pull-down resistor. vout 2 o this is the output of the dc-dc converter. fb 3 i this is the feedback pin of the device. the feedback pin measures the led current through the sense resistor. the feedback voltage is set internally to 500mv. iok 4 o this pin indicates that the dc-dc converter is ready for high current operation (open drain output). gnd 5, 7 control / logic ground. pvin 6 i this is the input voltage pin of the device. connect directly to the input bypass capacitor. vin 8 i this pin needs to be tied to the input voltage pin of the device. sw 9 i this is the switching pin of the converter. pgnd 10 power ground. powerpad? must be soldered to achieve appropriate power dissipation. should be connected to pgnd. 4 fb iok gnd pvin sw vout gnd vin en pgnd drc package (t op view) www .ti.com
tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 functional block diagram (tps61058/9) 5 vmax control gate control regulator error- amplifier v ref oscillator pgnd pvin sw vout fb gnd en pgnd gnd vin ovp v ref en control logic pgnd 20 pf t emperature control 10 k w iok 400 k w www .ti.com
parameter measurement information typical characteristics tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 table of graphs figure (tps61058) led power efficiency vs. input voltage 3 (tps61059) led power efficiency vs. input voltage 4 (tps61058) led power efficiency vs led current 5 (tps61058) dc input current vs. input voltage 6 (tps61058) led current vs. input voltage 7 oscillator frequency 8 (tps61059) current limit vs. temperature 9 waveforms switching waveforms in boost mode (tps61058) 10 switching waveforms in down-mode (tps61058) 11 high current flashlight pulse waveform (tps61058) 12 torch to flashlight transistion (tps61058) 13 start-up after enable (tps61058) 14 overvoltage protection (tps61058) 15 duty cycle jitter (tps61058) 16 6 c in l1 v in 22 f m 4.7 f m 2.7 v . . 5.5 v gnd tps61058/9 gnd p v in en vin sw vout fb pgnd c 1 , c2, c3 x3 d1 c3 r s r2 r1 iok r3 r 4 t orch on (0/1.8 v) 22 f m 22 k w 1 nf (cog) r6 r5 flash (0 . .2 v) 500 ma flashlight application rs = 1.3r2 = 56 k r3 = 100 k r4 = 2.4 k r5 = 6.2 k r6 = 91 k w w w ww w 700 ma flashlight application rs = 1.2r2 = 47 k r3 = 51 k r4 = 3.3 k r5 = 4.3 k r6 = 120 k w ww ww w list of components:l1 = tdk vlf5014a t -4r7 t c1,c2,c3 = tdk c2012x5r0j226mtj c4 (optional) c4 = 100 nf www .ti.com
tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 tps61058 tps61059 led power efficiency led power efficiency vs vs input voltage input voltage figure 3. figure 4. tps61058 tps61058 efficiency dc input current vs vs led current input voltage figure 5. figure 6. 7 0 10 20 30 40 50 60 70 80 90 100 2.70 3.10 3.50 3.90 4.30 4.70 5.50 v i ? input v oltage ? v led power efficiency (p led /p in ) ? % i l e d = 700 ma @ v f = 3.4 v i l e d = 150 ma @ v f = 3.0 v 5.10 0 200 400 600 800 1000 1200 1400 2.70 3.10 3.50 3.90 4.30 4.70 5.10 5.50 input dc current - ma v - input v oltage - v i i = 500 ma l ed 0 10 20 30 40 50 60 70 80 90 100 100 150 200 250 300 350 400 450 500 led current - ma led power efficiency (p /p ) - % l ed i n v = 3.3 v i n v = 4.2 v i n v = 3.6 v i n 0 10 20 30 40 50 60 70 80 90 100 2.70 3.10 3.50 3.90 4.30 4.70 5.10 5.50 l e d p o w e r e f f i c i e n c y ( p / p ) - % l e d i n i = 500 ma @ v = 3.7 v l ed f i = 150 ma @ v = 3.4 v l ed f v - input v oltage - v i www .ti.com
tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 tps61058 oscillator frequency led current vs input voltage figure 7. figure 8. tps61059 tps61058 current limit switching waveforms in boost mode vs temperature figure 9. figure 10. 8 0 2 4 6 8 10 12 14 16 606615 622 629636 643 650 657664 672 f ? oscillator frequency ? khz percent of units ? % t a = 25 c switch current limit ! a m ambient t emperature ! c 1250 1350 1450 1550 1650 1750 -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 sw (2 v/div) v = 3.6 v , i = 500 ma i l ed i (200 ma/div) l v (10 mv/div - 3.8 v offset) o u t i (200 ma/div) l ed t - t ime - 500 ns/div 0 100 200 300 400 500 600 2.70 3.10 3.50 3.90 4.30 4.70 5.10 5.50 led current - ma i = 500 ma l ed i = 150 ma l ed v - input v oltage - v i www .ti.com
tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 tps61058 tps61058 switching waveforms in down mode high current flashlight pulse waveform figure 11. figure 12. tps61058 tps61058 torch to flashlight transistion start-up after enable figure 13. figure 14. 9 en (1 v/div) t - t ime - 5 ms/div i (200 ma/div) l v (1 v/div) o u t i (200 ma/div) l ed v = 3.6 v i v (1 v/div) o u t i (200 ma/div) l ed i (500 ma/div) l t - t ime - 50 s/div m en (1 v/div) v (1 v/div) o u t i (50 ma/div) l ed i (100 ma/div) l t - t ime - 200 s/div m sw(2 v/div) i ( 2 0 0 m a / d i v ) l i ( 2 0 0 m a / d i v ) l e d v(10 mv/div - 3.8 v offset) o u t v = 4.5 v , i = 500 ma i l ed t - t ime - 500 ns/div www .ti.com
tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 tps61058 tps61058 overvoltage protection duty cycle jitter figure 15. figure 16. 10 v (200 mv/div - 5 v offset) o u t t - t ime - 50 ms/div sw (2 v/div) v = 3.6 v i i = 500 ma l ed t riggered on falling edge t - t ime - 50 ns/div www .ti.com
detailed description operation synchronous rectifier down regulation enable tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 the tps61058/9 familly is based on a fixed frequency multiple feedforward controller topology. input voltage, output voltage, and voltage drop on the nmos switch are monitored and forwarded to the regulator. so changes in the operating conditions of the converter directly affect the duty cycle and must not take the indirect and slow way through the control loop and the error amplifier. the control loop, determined by the error amplifier, only has to handle small signal errors. the input for it is the feedback voltage on the fb pin. it is compared with the internal reference voltage to generate an accurate and stable led current. the peak current of the nmos switch is also sensed to limit the maximum current flowing through the switch and the inductor. the typical peak current limit is set to 1000ma (tps61058) and 1500 ma (tps61059). an internal temperature sensor prevents the device from getting overheated in case of excessive power dissipation. the device integrates an n-channel and a p-channel mosfet transistor to realize a synchronous rectifier. because the commonly used discrete schottky rectifier is replaced with a low rds(on) pmos switch, the power conversion stage itself can reach 96% efficiency. in order to avoid ground shift due to the high currents in the nmos switch, two separate ground pins are used. the reference for all control functions is the gnd pin. the source of the nmos switch is connected to pgnd. both grounds must be connected on the pcb at only one point close to the gnd pin. a special circuit is applied to disconnect the load from the input during shutdown of the converter. in conventional synchronous rectifier circuits, the backgate diode of the high-side pmos is forward biased in shutdown and allows current flow from the battery to the output. this device however uses a special circuit which takes the cathode of the backgate diode of the high-side pmos and disconnects it from the source when the regulator is not enabled (en = low). the benefit of this feature for the system design engineer is that the battery is not depleted during shutdown of the converter. no additional components have to be added to the design to make sure that the battery is disconnected from the output of the converter. in general, a boost converter only regulates output voltages which are higher than the input voltage. this device operates differently and is capable of driving high power single die white leds from a fully charged li-ion cell. to control this applications properly, a down conversion mode is implemented. if the input voltage reaches or exceeds the output voltage necessary to maintain the led current within regulation, the converter changes to a down conversion mode. in this mode, the control circuit changes the behavior of the rectifying pmos transitor. it sets the voltage drop across the pmos as high as needed to regulate the output voltage. this means the power losses in the converter increase. this has to be taken into account for thermal consideration especially when operating with low v f leds, high battery voltages and high led currents. the device is put into operation when en is set high. it is put into a shutdown mode when en is set to gnd. the en input pin has an internal 400-k w pull-down resistor to disable the device when this pin is floating. in shutdown mode, the regulator stops switching, the internal control circuitry is switched off, and the load is isolated from the input (as described in the synchronous rectifier section). this also means that the output voltage can drop below the input voltage during shutdown. 11 www .ti.com
softstart overvoltage protection (ovp) efficiency and sense voltage thermal shutdown tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 detailed description (continued) to avoid high inrush current during start-up, special care is taken to control the inrush current. when the device is first enabled, the output capacitor is charged with a constant pre-charge current of 115ma (typ) until either the output voltage is typically 0.1v below the input voltage or the feedback voltage is 500mv (typ). the rectifying switch is current limited during the pre-charge phase. this also limits the output current under short circuit conditions at the output. the fixed pre-charge current during start-up allows the device to start up without problems when driving single die white leds as long as the led start-up current is set to a value lower than the pre-charge current (84 ma min.). refer to the application section for more details. when the device has finished start-up and is ready for high current operation, the device forces iok output to ground, starts switching and regulates the led current to the desired value (e.g. torch or flashlight current level). as with any current source, the output voltage rises when the load becomes high impedance or gets disconnected. to prevent the output voltage exceeding the maximum switch voltage rating (7 v) of the main switch, an overvoltage protection circuit is integrated. as soon as the output voltage exceeds the ovp threshold, the converter stops switching and the output voltage decreases. when the output voltage falls below the ovp threshold, the converter continues operation until the output voltage exceeds the ovp threshold again. the voltage across the sense resistor (r s ) has a direct effect of the converter efficiency. because the sense voltage does not contribute to the output power (p led ), the lower this voltage the higher the efficiency. it is therefore recommended to operate with a sense voltage of approximately 0.75v at maximum led current. an internal thermal shutdown is implemented and turns off the internal mosfets when the typical junction temperature of 140 c is exceeded. the thermal shutdown has a hysteresis of typically 20 c. refer to the thermal information section. 12 www .ti.com
application information design procedure (1) tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 the standard application circuit (figure 17 ) of the tps61058/9 is a complete solution to drive high-power white leds with two discrete current steps. figure 18. waveform profiles figure 17. typical application the led current is programmed using external resistors (r s , r2, r3, r4, r5, and r6). the first step to turn on the led is to enable the device (en = high). after charging the output capacitor, the device forces iok to ground, starts switching, and regulates the led current to the desired value. the control signal, nflash, injects current into the feedback network through r4, thereby, changing the led current. for this reason, the nflash control signal needs at least to be biased up until iok goes low. in case this is not done properly the converter stays stuck in the pre-chage phase. to faciliate the sizing of the external resistor network, it is recommended to use the calculation sheet available in the device product folder. 1. sense resistor, r s the voltage across the sense resistor should be set to approximately 0.75 v at maximum led current. check the power rating of the sense resistor (p d = r s i led 2 ). 2. led current setting figure 19 shows an equivalent circuit for the feedback network. the regulation loop is using an external control voltage (nflash) to set the led current. with the help of this voltage the feedback bias current (i bias ) can be adjusted which, in effect, controls the led current without changing any externals. in most applications a variable control voltage is not available to set the led current. in practical applications, nflash can either be: a constant bias voltage (2.8 v for example) which in combination with iok can be used to switch between two led currents (off, flashlight). a logic signal generated by the imaging processor. this configuration permits three different led currents: off, movie-light (nflash = high), flashlight (nflash = low). 13 nflash iok iled flashlight movie-light hi-z hi-z pre-charge movie-light gnd c in l 1 gnd pvinen vin sw vout fb pgnd v in d 1 r s r 2 r 3 r 4 nflash iok vx r 6 r5 2.7 v . . 5.5 v 4.7 m h 22 m f movie-light c1, c2, c3 22 m f x3 c4 1 nf (cog) r122 k w v sense tps61058/9 c5 100nf r s v s e n s e i l e d www .ti.com
(2) (3) (4) (5) (6) (7) (8) tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 the circuit operation can be split into different phases: 1. pre-charge phase (iok = hi-z) during this phase iok is kept high-impedance. for proper startup the external loop components need to be chosen so that the regulation loop can settle for a maximum led current of less than 84 ma. this can be achieved by increasing the bias voltage (v x ) of the feedback network. 2. high-current operation (iok = gnd) after the pre-charge phase, iok is automatically pulled to ground. this modifies the feedback divider network changing the potential of the v x node. as a consequence the led current is adjusted accordingly. for operation at maximum led current (flashlight mode), nflash needs to be set to ground level. for operation at other led currents (movie-light or pre-charge), nflash applies a positive bias voltage (1.8 v for example) to the feedback divider network. the following equations show the relationship between led current and bias voltage vx. for stable operation, it is recommended that r3 be set in the range of 50 k w to 150 k w and r5 in the range of 3.3 k w to 10 k w . best performance is obtained with a pre-charge current of 45 ma typ. for single current level applications (e.g. torch or flashlight only) it is recommended to operate with r4 in the range of 50k w to 200 k w . in that case r5 is not need anymore. 14 i l e d 0 . 5 r 2 i b i a s r s i l e d ( f l a s h ) r 2 r 3 2 r 3 r s , a s s u m i n g r 4 r 5 r 6 i s s m a l l c o m p a r e d r 3 . i b i a s 2 r 5 r 3 ( r 4 r 5 ) n f l a s h 0 . 5 r 3 , w i t h r 5 r 5 r 6 r 5 r 6 i l e d 0 . 5 r 2 i b i a s 2 r s 1 2 r s r 2 2 r 3 r s r 2 r 3 r s v x i b i a s r 5 r 3 ( r 4 r 5 ) n f l a s h 0 . 5 r 3 , a s s u m i n g r 4 r 5 i s s m a l l c o m p a r e d r 3 . www .ti.com v x r 5 r 4 r 5 n f l a s h , w i t h r 5 r 5 r 6 r 5 r 6 v x 12 r 3 2 r 2 i l e d ( m o v i e l i g h t , p r e c h a r g e ) r 3 r s r 2
(9) (10) (11) (12) (13) tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 the following example is used to explain the procedure to size the external components for a given set of requirements: movie-light mode: i led = 150 ma flashlight mode: i led = 500 ma led forward voltage: v f (max) = 4.4 v at 500 ma nflash signal is 1.8 v logic compliant (0 v and 1.8 v 4%) step 1 ? current sense resistor calculation ? r s step 2 ? feedback divider resistor calculation ? r2, r3 step 3 ? bias resistor network calculation ? r4, r5, r6 during the pre-charge phase, iok is high impedance. in movie-light mode, iok is grounded. figure 19. feedback network equivalent circuit 15 www .ti.com iok m 1 r 4 nflash r 3 r 2 r s i led v x v sense r 6 r 5 i bias fb = 500 mv v x r 5 r 4 r 5 n f l a s h r 5 r 4 r 5 0 . 7 8 r 5 1 0 k ( r e c o m m e n d e d v a l u e ) r 4 2 . 7 k ( c a l c u l a t e d ) v x r 5 r 4 r 5 n f l a s h r 5 r 4 r 5 0 . 6 1 , r 5 1 . 5 7 r 4 , r 5 r 5 r 6 r 5 r 6 r 6 7 . 5 k ( c a l c u l a t e d ) v x 12 r 3 2 r 2 i l e d r 3 r s r 2 v x 1 . 1 v @ i l e d 1 5 0 m a ( m o v i e ? l i g h t ) v x 1 . 4 v @ i l e d 4 5 m a ( p r e ? l o a d ) r s v s e n s e i l e d 0 . 7 5 0 . 5 1 . 5 v o u t ( m a x ) 4 . 4 0 . 7 5 5 . 1 5 v i l e d ( f l a s h ) r 2 r 3 2 r 3 r s r 3 1 0 0 k ( r e c o m m e n d e d v a l u e ) r 2 4 7 k ( c a l c u l a t e d )
inductor selection (14) (15) (16) tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 a boost converter normally requires two main passive components for storing energy during the conversion. a boost inductor and a storage capacitor at the output are required. to select the boost inductor, it is recommended to keep the possible peak inductor current below the current limit threshold of the power switch in the chosen configuration. for example, the current limit threshold of the tps61059 switch is 1700 ma at an output voltage of 5 v. the highest peak current through the inductor and the switch depends on the output load, the input voltage and the output voltage. estimation of the maximum average inductor current can be done using equation 14 : for example, for an output current of 500 ma at 4.5 v, at least 800 ma of average current flows through the inductor at a minimum input voltage of 3.3 v. the second parameter for choosing the inductor is the desired current ripple in the inductor. in order to optimized the solution size, inductor ripple currents as high as 40% of the average inductor current can be tolerated. a smaller ripple reduces the magnetic hysteresis losses in the inductor, as well as output voltage ripple and emi. with those parameters, it is possible to calculate the value for the inductor by using equation 16 : parameter f is the switching frequency and d i l is the ripple current in the inductor, i.e., 40% i l . in this example, the desired inductor has the value of 4.5 h. with this calculated value and the calculated currents, it is possible to choose a suitable inductor. in typical high current white led applications a 4.7 h inductance is recommended. care has to be taken that load transients and losses in the circuit can lead to higher currents as estimated in equation 16 . also, the losses in the inductor caused by magnetic hysteresis losses and copper losses are a major parameter for total circuit efficiency. the following inductor series from different suppliers have been used with the tps61058/9 converters: table 1. list of inductors manufacturer series dimensions remarks coilcraft lps3015 3 mm x 3 mm x 1.5 mm max. height tps61058 vlf3014at 2.6 mm x 2.8 mm x 1.4 mm max. height tps61058 tdk vlf5014at 4.5 mm x 4.7 mm x 1.4 mm max. height tps61059 taiyo yuden np04szb 5 mm x 5 mm x 2.0 mm max. height tps61059 16 www .ti.com i l i o u t v o u t v i n 0 . 8 v o u t v f ( l e d ) r s i l e d l v i n v o u t v i n i l ? v o u t
capacitor selection input capacitor output capacitor (17) (18) checking loop stability tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 for good input voltage filtering low esr ceramic capacitors are recommended. at least a 10-f input capacitor is recommended to improve transient behavior of the regulator and emi behavior of the total power supply circuit. the input capacitor should be placed as close as possible to the input pin of the converter. the major parameter necessary to define the output capacitor is the maximum allowed output voltage ripple of the converter. this ripple is determined by two parameters of the capacitor, the capacitance and the esr. it is possible to calculate the minimum capacitance needed for the defined ripple, supposing that the esr is zero, by using equation 17 : parameter f is the switching frequency and d v is the maximum allowed ripple. with a chosen ripple voltage of 10 mv, a minimum capacitance of 22 f is needed. the total ripple is larger due to the esr of the output capacitor. this additional component of the ripple can be calculated using equation 18 : the total ripple is the sum of the ripple caused by the capacitance and the ripple caused by the esr of the capacitor. additional ripple is caused by load transients. this means that the output capacitor has to completely supply the load during the charging phase of the inductor. a reasonable value of the output capacitance depends on the speed of the load transients and the load current during the load change. for the high current white led application, a minimum of 20 f effective output capacitance is usually required when operating with 4.7 h (typ) inductors. for solution size reasons, this is usually one or more x5r/x7r ceramic capacitors. in order to maintain the control loop stable, the addition of a compensation network formed by r1 (22 k w ) and c3 (1 nf cog) is necessary. the first step of circuit and stability evaluation is to look from a steady-state perspective at the following signals: switching node, sw inductor current, i l output ripple voltage, v out(ac) these are the basic signals that need to be measured when evaluating a switching converter. when the switching waveform shows large duty cycle jitter or the output voltage or inductor current shows oscillations, the regulation loop may be unstable. this is often a result of board layout and/or l-c combination. as a next step in the evaluation of the regulation loop, the load transient response is tested. v out can be monitored for settling time, overshoot or ringing that helps judge the converter's stability. without any ringing, the loop has usually more than 45 of phase margin. because the damping factor of the circuitry is directly related to several resistive parameters (e.g., mosfet r ds(on) ) that are temperature dependant, the loop stability analysis has to be done over the input voltage range, led current range, and temperature range. 17 www .ti.com c m i n i o u t v o u t v i n ? v v o u t v e s r i o u t r e s r
layout considerations tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 as for all switching power supplies, the layout is an important step in the design, especially at high peak currents and high switching frequencies. if the layout is not carefully done, the regulator could show stability problems as well as emi problems. therefore, use wide and short traces for the main current path and for the power ground tracks. the input capacitor, output capacitor, and the inductor should be placed as close as possible to the ic. use a common ground node for power ground and a different one for control ground to minimize the effects of ground noise. connect these ground nodes at any place close to one of the ground pins of the ic. the compensation network as well as the current setting resistors should be placed as close as possible to the control ground pin of the ic. to lay out the control ground, it is recommended to use short traces as well, separated from the power ground traces. this avoids ground shift problems, which can occur due to superimposition of power ground current and control ground current. figure 20. suggested layout ? top side figure 21. suggested layout ? bottom side 18 www .ti.com
application examples tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 figure 22. 500 ma flashlight application - 1.8 v logic figure 23. 150 ma movie-light/600 ma flashlight application - 2.8 v logic 19 www .ti.com c in l1 v in 22 f 4.7 h 2.7 v . . 5.5 v gnd tps61058 gnd pvin en vin sw vout fb pgnd c1, c2, c3 x3 d1 c3 r s r2 r1 iok r3 r4 flash on (0/1.8 v) 22 f 39 k 22 k 56 k 1.5 68 k 1 nf(cog) r6 5.6 k list of components:l1 = coilcraft lps3015?4r7 c1,c2, c3 = tdk c2012x5r0j226mtj gnd c in l1 tps61059 gnd pvinen vin sw vout fb pgnd c 1 , c2, c3 x3 v in d1 c 4 r s r2 1n f (cog) list of components:l1 = tdk vlf5014a t?4r7 c1,c2, c3 = tdk c2012x5r0j226mtj movie ? light nflash iled 0 0 off 0 1 off 1 0 flashlight 1 1 movie ? light r 6 iok 22 f 33 k 1.2 r43.9 k 10 k r122 k 4.7 h 2.7 v . . 5.5 v 22 f r375 k movie?light (0/2.8v) nflash (0/2.8v) r 5 4.7 k c5 100 nf note: before turning into the flashlight mode, thedevice to be driven into movie?light mode. see the design procedure section for more details.
tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 figure 24. 500 ma flashlight application - 2.8 v logic figure 25. 150 ma movie-light/700 ma flashlight with no-latency current reduction 20 www .ti.com gnd c in l1 tps61058 gnd pvinen vin sw vout fb pgnd c 1 , c2, c3 x3 v in d1 c4 r s r2 r1 1n f (cog) iok list of components:l1 = coilcraft lps3015?4r7 c1,c2, c3 = tdk c2012x5r0j226mtj r 6 1.5 r4150 k 4.7 h r351 k flash on (0/2.8v) 22 f 22 f 39 k 10 k 22 k 2.7 v . . 5.5 v 22 f 4.7 h gnd c in l1 tps61059 gnd pvinen vin sw vout fb pgnd c 1 , c2, c3 x3 v in d1 c 4 r s r2 r1 1n f (cog) r 3 r 4 movie?light (0/1.8 v) list of components:l1 = tdk vlf5014a t?4r7 c1,c2, c3 = tdk c2012x5r0j226mtj tx?t off (0/1.8 v) iok n flash (0/1.8 v) l vc1g32 1v8 68 k 100 k 3.6 k 22 k 22 f 2.7 v . . 5.5 v 1.2 r 6 12 k r5 6.8 k c5 100nf
tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 figure 26. 2x 350 ma flashlight application - 2.8 v logic 21 www .ti.com gnd c in l1 tps61059 gnd pvinen vin sw vout fb pgnd c 1 , c2, c3 x3 v in d1 c3 r1 r4 r1 1n f (cog) iok list of components:l1 = tdk vlf5014a t?4r7 c1,c2, c3 = tdk c2012x5r0j226mtj r 7 2.0 r61 10 k 4.7 h r575 k flash on (0/2.8v) 22 f 22 f 75 k 5.1 k 22 k 2.7 v . . 5.5 v r2 2.0 r 3 75 k d2 v1 v2 c5 100 nf
thermal information (19) tps61058 tps61059 slvs572b ? april 2005 ? revised december 2005 implementation of integrated circuits in low-profile and fine-pitch surface-mount packages typically requires special attention to power dissipation. many system-dependent issues such as thermal coupling, airflow, added heat sinks and convection surfaces, and the presence of other heat-generating components affect the power-dissipation limits of a given component. three basic approaches for enhancing thermal performance are listed below. improving the power dissipation capability of the pcb design improving the thermal coupling of the component to the pcb introducing airflow in the system the maximum recommended junction temperature (t j ) of the tps61058/9 devices is 125 c. the thermal resistance of the 10-pin qfn 3 x 3 package (drc) is r q ja = 48.7 c/w, if the powerpad is soldered. specified regulator operation is assured to a maximum ambient temperature t a of 85 c. therefore, the maximum power dissipation is about 820 mw. more power can be dissipated if the maximum ambient temperature of the application is lower. 22 www .ti.com p d ( m a x ) t j ( m a x ) t a r j a 1 2 5 c 8 5 c 4 8 . 7 c w 8 2 0 m w
packaging information orderable device status (1) package type package drawing pins package qty eco plan (2) lead/ball finish msl peak temp (3) tps61058drcr active son drc 10 3000 green (rohs & no sb/br) cu nipdau level-2-260c-1 year tps61058drcrg4 active son drc 10 3000 green (rohs & no sb/br) cu nipdau level-2-260c-1 year tps61059drcr active son drc 10 3000 green (rohs & no sb/br) cu nipdau level-2-260c-1 year tps61059drcrg4 active son drc 10 3000 green (rohs & no sb/br) cu nipdau level-2-260c-1 year tps61059drct active son drc 10 250 green (rohs & no sb/br) cu nipdau level-2-260c-1 year TPS61059DRCTG4 active son drc 10 250 green (rohs & no sb/br) cu nipdau level-2-260c-1 year (1) the marketing status values are defined as follows: active: product device recommended for new designs. lifebuy: ti has announced that the device will be discontinued, and a lifetime-buy period is in effect. nrnd: not recommended for new designs. device is in production to support existing customers, but ti does not recommend using this part in a new design. preview: device has been announced but is not in production. samples may or may not be available. obsolete: ti has discontinued the production of the device. (2) eco plan - the planned eco-friendly classification: pb-free (rohs), pb-free (rohs exempt), or green (rohs & no sb/br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. tbd: the pb-free/green conversion plan has not been defined. pb-free (rohs): ti's terms "lead-free" or "pb-free" mean semiconductor products that are compatible with the current rohs requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. where designed to be soldered at high temperatures, ti pb-free products are suitable for use in specified lead-free processes. pb-free (rohs exempt): this component has a rohs exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. the component is otherwise considered pb-free (rohs compatible) as defined above. green (rohs & no sb/br): ti defines "green" to mean pb-free (rohs compatible), and free of bromine (br) and antimony (sb) based flame retardants (br or sb do not exceed 0.1% by weight in homogeneous material) (3) msl, peak temp. -- the moisture sensitivity level rating according to the jedec industry standard classifications, and peak solder temperature. important information and disclaimer: the information provided on this page represents ti's knowledge and belief as of the date that it is provided. ti bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. efforts are underway to better integrate information from third parties. ti has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. ti and ti suppliers consider certain information to be proprietary, and thus cas numbers and other limited information may not be available for release. in no event shall ti's liability arising out of such information exceed the total purchase price of the ti part(s) at issue in this document sold by ti to customer on an annual basis. package option addendum www.ti.com 5-feb-2007 addendum-page 1
tape and reel information package materials information www.ti.com 17-may-2007 pack materials-page 1
device package pins site reel diameter (mm) reel width (mm) a0 (mm) b0 (mm) k0 (mm) p1 (mm) w (mm) pin1 quadrant tps61058drcr drc 10 mla 330 12 3.3 3.3 1.1 8 12 pkgorn t2tr-ms p tps61059drcr drc 10 mla 330 12 3.3 3.3 1.1 8 12 pkgorn t2tr-ms p tps61059drct drc 10 mla 180 12 3.3 3.3 1.1 8 12 pkgorn t2tr-ms p tape and reel box information device package pins site length (mm) width (mm) height (mm) tps61058drcr drc 10 mla 346.0 346.0 29.0 tps61059drcr drc 10 mla 346.0 346.0 29.0 tps61059drct drc 10 mla 190.0 212.7 31.75 package materials information www.ti.com 17-may-2007 pack materials-page 2
package materials information www.ti.com 17-may-2007 pack materials-page 3

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