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1 LT1008 picoamp input current, microvolt offset, low noise op amp the lt ? 1008 is a universal precision operational amplifier that can be used in practically all precision applications. the LT1008 combines for the first time, picoampere bias currents (which are maintained over the full C 55 c to 125 c temperature range), microvolt offset voltage (and low drift with time and temperature), low voltage and current noise, and low power dissipation. extremely high common mode and power supply rejection ratios, and the ability to deliver 5ma load current with high voltage gain round out the LT1008s superb precision specifications. the all around excellence of the LT1008 eliminates the necessity of the time consuming error analysis procedure of precision system design in many applications; the LT1008 can be stocked as the universal precision op amp. the LT1008 is externally compensated with a single ca- pacitor for additional flexibility in shaping the frequency response of the amplifier. it plugs into and upgrades all standard lm108a/lm308a applications. for an internally compensated version with even lower offset voltage but otherwise similar performance see the lt1012. n guaranteed bias current t a = 25 c: 100pa max t a = C 55 c to 125 c: 600pa max n guaranteed offset voltage: 120 m v max n guaranteed drift: 1.5 m v/ c max n low noise, 0.1hz to 10hz: 0.5 m v p-p n guaranteed low supply current: 600 m a max n guaranteed cmrr: 114db min n guaranteed psrr: 114db min n guaranteed voltage gain with 5ma load current n precision instrumentation n charge integrators n wide dynamic range logarithmic amplifiers n light meters n low frequency active filters n standard cell buffers n thermocouple amplifiers input amplifier for 4.5 digit voltmeter features descriptio u applicatio s u typical applicatio u + LT1008 1 1000pf 2 3 100k 5% 8 4 7 15v 15v 6 0.1v input 1v 10v 10v 1v 100v 1000v 1008 ta01 to 1v full-scale analog-to-digital converter *ratio match 0.01% 9m 100v 900k 9k* 0.1v 1k* 1000v fn507 allen bradley decade voltage divider this application requires low bias current and offset voltage, low noise and low drift with time and temperature 90k 10k temperature ( c) ?0 ?50 input bias current (pa) ?0 100 0 50 75 1008 ta02 ?00 50 0 ?5 25 100 125 undercancelled unit overcancelled unit input bias current vs temperature , ltc and lt are registered trademarks of linear technology corporation.
2 LT1008 (note 1) supply voltage ...................................................... 20v differential input current (note 2) ..................... 10ma input voltage ........................................................ 20v output short-circuit duration ......................... indefinite storage temperature range ................. C 65 c to 150 c absolute axi u rati gs w ww u package/order i for atio uu w order part number LT1008mh LT1008ch t jmax = 150 c, q ja = 150 c/w, q jc = 45 c/w t jmax = 150 c, q ja = 130 c/w operating temperature range LT1008m (obsolete) ............... C55 c to 125 c LT1008c ................................................. 0 c to 70 c LT1008i ............................................. C 40 c to 85 c lead temperature (soldering, 10 sec).................. 300 c top view v + comp2 comp1 ?n out nc +in v ? (case) 8 7 6 5 3 2 1 4 h package 8-lead to-5 metal can + 1 2 3 4 8 7 6 5 top view comp1 ?n +in v comp2 v + out nc n8 package 8-lead pdip LT1008mj8 LT1008cj8 j8 package 8-lead cerdip t jmax = 150 c, q ja = 100 c/w 1 2 3 4 8 7 6 5 top view comp2 v + out nc comp1 ?n +in v s8 package 8-lead plastic so t jmax = 150 c, q ja = 190 c/w obsolete packages order part number LT1008s8 s8 part marking 1008 LT1008m/i LT1008c symbol parameter conditions min typ max min typ max units v os input offset voltage 30 120 30 120 m v (note 3) 40 180 40 180 m v long-term input offset voltage stability 0.3 0.3 m v/month i os input offset current 30 100 30 100 pa (note 4) 40 150 40 150 pa i b input bias current 30 100 30 100 pa (note 5) 40 150 40 150 pa e n input noise voltage 0.1hz to 10hz 0.5 0.5 m v p-p input noise voltage density f o = 10hz (note 4) 17 30 17 30 nv ? hz f o = 1000hz (note 5) 14 22 14 22 nv/ ? hz i n input noise current density f o = 10hz 20 20 fa/ ? hz a vol large-signal voltage gain v out = 12v, r l 3 10k 200 2000 200 2000 v/mv v out = 10v, r l 3 2k 120 600 120 600 v/mv electrical characteristics v s = 15v, v cm = 0v, t a = 25 c, unless otherwise noted. consult ltc marketing for parts specified with wider operating temperature ranges. order part number LT1008cn8 LT1008in8 order part number consider n8 or s8 package for alternate source
3 LT1008 the l indicates specifications which apply over the full operating temperature range of C 55 c t a 125 c for the LT1008m, C 40 c t a 85 c for the LT1008i and 0 c t a 70 c for the LT1008c. v s = 15v, v cm = 0v, unless otherwise noted. LT1008m/i LT1008c symbol parameter conditions min typ max min typ max units v os input offset voltage l 50 250 40 180 m v (note 3) l 60 320 50 250 m v average temperature coefficient of input offset voltage l 0.2 1.5 0.2 1.5 m v/ c i os input offset current l 60 250 40 180 pa (note 3) l 80 350 50 250 pa average temperature coefficient of input offset current l 0.4 2.5 0.4 2.5 pa/ c i b input bias current l 80 600 40 180 pa (note 3) l 150 800 50 250 pa average temperature coefficient of input bias current l 0.6 6 0.4 2.5 pa/ c a vol large-signal voltage gain v out = 12v, r l 3 10k l 100 1000 150 1500 v/mv cmrr common mode rejection ratio v cm = 13.5v l 108 128 110 130 db psrr power supply rejection ratio v s = 2.5v to 20v l 108 126 110 128 db input voltage range l 13.5 13.5 v v out output voltage swing r l = 10k l 13 14 13 14 v i s supply current l 400 800 400 800 m a electrical characteristics v s = 15v, v cm = 0v, t a = 25 c, unless otherwise noted. LT1008m/i LT1008c symbol parameter conditions min typ max min typ max units cmrr common mode rejection ratio v cm = 13.5v 114 132 114 132 db psrr power supply rejection ratio v s = 2v to 20v 114 132 114 132 db input voltage range 13.5 14 13.5 14 v v out output voltage swing r l = 10k 13 14 13 14 v slew rate c f = 30pf 0.1 0.2 0.1 0.2 v/ m s i s supply current (note 3) 380 600 380 600 m a symbol parameter conditions min typ max units v os input offset voltage 30 200 m v (note 3) 40 250 m v long-term input offset voltage stability 0.3 m v/month i os input offset current 100 280 pa (note 3) 120 380 pa i b input bias current 100 300 pa (note 3) 120 400 pa e n input noise voltage 0.1hz to 10hz 0.5 m v p-p input noise voltage density f o = 10hz (note 5) 17 30 nv/ ? hz f o = 1000hz (note 5) 14 22 nv/ ? hz (LT1008s8 only) v s = 15v, v cm = 0v, t a = 25 c, unless otherwise noted.
4 LT1008 symbol parameter conditions min typ max units i n input noise current density f o = 10hz 20 fa/ ? hz a vol large-signal voltage gain v out = 12v, r l 3 10k 200 2000 v/mv v out = 10v, r l 3 2k 120 600 v/mv cmrr common mode rejection ratio v cm = 13.5v 110 132 db psrr power supply rejection ratio v s = 2v to 20v 110 132 db input voltage range 13.5 14 v v out output voltage swing r l = 10k 13 14 v slew rate c f = 30pf 0.1 0.2 v/ m s i s supply current (note 3) 380 600 m a electrical characteristics (LT1008s8 only) v s = 15v, v cm = 0v, t a = 25 c, unless otherwise noted. (LT1008s8 only) the l indicates specifications which apply over the full operating temperature range of 0 c t a 70 c. v s = 15v, v cm = 0v, unless otherwise noted. symbol parameter conditions min typ max units v os input offset voltage l 40 280 m v (note 3) l 50 340 m v average temperature coefficient of l 0.2 1.8 m v/ c input offset voltage i os input offset current l 120 380 pa (note 3) l 140 500 pa average temperature coefficient of l 0.4 4 pa/ c input offset current i b input bias current l 120 420 pa (note 3) l 140 550 pa average temperature coefficient of l 0.4 5 pa/ c input bias current a vol large-signal voltage gain v out = 12v, r l 3 10k l 150 1500 v/mv cmrr common mode rejection ratio v cm = 13.5v l 108 130 db psrr power supply rejection ratio v s = 2.5v to 20v l 108 128 db input voltage range l 13.5 v v out output voltage swing r l = 10k l 13 14 v i s supply current l 400 800 m a note 1: absolute maximum ratings are those values beyond which the life of a device may be impaired. note 2: differential input voltages greater than 1v will cause excessive current to flow through the input protection diodes unless current limiting resistors are used. note 3: these specifications apply for 2v v s 20v ( 2.5v v s 20v over the temperature range) and C13.5v v cm 13.5v (for v s = 15v). note 4: 10hz noise voltage density is sample tested on every lot. devices 100% tested at 10hz are available on request. note 5: this parameter is tested on a sample basis only.
5 LT1008 typical perfor a ce characteristics uw offset voltage drift vs source resistance (balanced or unbalanced) input bias current vs common mode range warm-up drift long-term stability of four representative units offset voltage drift with temperature of four representative units source resistance ( w ) 1k 10k 0.1 offset voltage drift with temperature ( v/ c) 10 100 100k 1m 10m 100m 1008 g01 1 maximum typical source resistance ( w ) 1k 10k 0.01 input offset voltage (mv) 1 10 100k 1m 10m 100m 1008 g02 0.1 maximum typical v s = 15v t a = 25 c common mode input voltage (v) ?5 ?0 input bias current (pa) ?0 ?0 0 20 60 ?0 ? 0 5 1008 g03 10 15 40 + i b v cm device with positive input current device with negative input current v s = 15v t a = 25 c r incm = 2 10 12 offset voltage vs source resistance (balanced or unbalanced) temperature ( c) ?0 offset voltage ( v) 20 40 60 25 75 1008 g06 0 ?0 ?5 0 50 100 125 ?0 ?0 time (months) 0 change in offset voltage ( v) 2 6 10 4 1008 g05 ? ? 0 4 8 ? ? ?0 1 2 3 5 time after power on (minutes) 0 change in offset voltage ( v) 3 4 5 4 1008 g04 2 1 0 1 2 3 5 metal can (h) package dual-in-line package plastic (n) or cerdip (j) v s = 15v t a = 25 c u w freque cy co pe satio circuits u u + LT1008 6 v out 1 8 r1c o r1 + r2 c f 3 c o = 30pf 2 3 **bandwidth and slew rate are proportional to 1/c f r3 c f ** r1 r2 +v in ? in 1008 fcc01 + LT1008 6 v out 1008 fcc02 8 2 3 **bandwidth and slew rate are proportional to 1/c s *improves rejection of power supply noise by a factor of 5 c s ** 100pf r1 r2 +v in ? in for > 200, no external frequency compensation is necessary r2 r1 standard compensation circuit alternate* frequency compensation
6 LT1008 typical perfor a ce characteristics uw 0.1hz to 10hz noise noise spectrum total noise vs source resistance voltage gain vs frequency gain, phase shift vs frequency with alternate compensation time (seconds) 0 noise voltage (400nv/div) 8 1008 g09 2 4 6 10 t a = 25 c v s = 2v to 20v frequency (hz) 1 1 voltage noise density (nv/ hz) current noise density (fa/ hz) 10 100 1000 10 100 1000 1008 g10 current noise voltage noise 1/f corner 2.5hz 1/f corner 120hz t a = 25 c v s = 2v to 20v source resistance ( ) 10 2 10 3 10 4 10 5 10 6 10 7 10 8 total noise density ( v/ hz) 0.1 1 10 1008 g11 0.01 t a = 25 c v s = 2v to 20v at 1hz resistor noise only at 10hz r r s = 2r r + at 10hz at 1hz frequency (hz) 0.01 0.1 voltage gain (db) 60 80 100 1m 1008 g12 40 20 ?0 1 100 10k 10m 10 1k 100k 0 140 120 c s = 10pf c f = 3pf c f = 30pf c s = 100pf frequency (mhz) 0.01 ?0 gain (db) phase shift (deg) 20 30 40 0.1 1 10 1008 g13 10 0 200 140 120 100 160 180 f c s = 10pf f c s = 100pf gain c s = 100pf gain c s = 10pf phase margin with c s = 100pf = 56 t a = 25 c v s = 15v gain, phase shift vs frequency with standard (feedback) compensation frequency (mhz) 0.01 ?0 gain (db) phase shift (deg) 20 30 40 0.1 1 10 1008 g14 10 0 200 140 120 100 160 180 f c f = 3pf f c f = 30pf gain c f = 30pf gain c f = 3pf phase margin with c f = 30pf = 60 t a = 25 c v s = 15v supply current vs supply voltage supply voltage ( v) 0 supply current ( a) 400 450 20 1008 g07 350 300 5 25 c 125 c ?5 c 10 15 500 output short-circuit current vs time time from output short (minutes) 0 ?5 sourcing short-circuit current (ma) sinking ?2 ? ? 0 15 6 1.0 2.0 2.5 1008 g08 ? 9 12 3 0.5 1.5 3.0 3.5 ?5 c ?5 c 125 c 125 c 25 c 25 c
7 LT1008 typical perfor a ce characteristics uw large-signal transient response slew rate vs compensation capacitance compensation capacitor (pf) slew rate (v/ s) 10 108 g19 0.1 1 20 100 80 60 40 0 c s c f v s = 15v t a = 25 c 2v/div a v = 1 20 m s/div 1008 g18 c s = 100pf large-signal transient response 2v/div a v = 1 20 m s/div 1008 g20 c f = 30pf small-signal transient response 20mv/div a v = 1 5 m s/div 1008 g21 c s = 100pf c load = 100pf small-signal transient response 20mv/div a v = 1 5 m s/div 1008 g22 c s = 100pf c load = 600pf small-signal transient response 20mv/div a v = 1 5 m s/div 1008 g23 c f = 30pf c load = 100pf voltage gain vs load resistance common mode rejection vs frequency power supply rejection vs frequency load resistance (k ) 12 5 100k 300k voltage gain 1m 3m 10m 10 20 1008 g15 ?5 c 25 c 125 c v s = 15v v o = 10v frequency (hz) 1 140 120 100 80 60 40 20 0 1k 100k 1008 g16 10 100 10k 1m common mode rejection ratio (db) c f = 30pf c s = 100pf v s = 15v t a = 25 c frequency (hz) 0.1 power supply rejection ratio (db) 100 120 140 100 10k 1008 g17 80 60 110 1k 100k 1m 40 20 negative supply v s = 15v t a = 25 c positive supply c f = 30pf positive supply c s = 100pf
8 LT1008 applicatio s i for atio wu uu achieving picoampere/microvolt performance in order to realize the picoamperemicrovolt level accu- racy of the LT1008, proper care must be exercised. for example, leakage currents in circuitry external to the op amp can significantly degrade performance. high quality insulation should be used (e.g., teflon tm , kel-f); cleaning of all insulating surfaces to remove fluxes and other residues will probably be required. surface coating may be necessary to provide a moisture barrier in high humidity environments. board leakage can be minimized by encircling the input circuitry with a guard ring operated at a potential close to that of the inputs: in inverting configurations the guard ring should be tied to ground, in noninverting connections to the inverting input at pin 2. guarding both sides of the printed circuit board is required. bulk leakage reduction depends on the guard ring width. nanoampere level leak- age into the compensation terminals can affect offset voltage and drift with temperature. the LT1008 is specified over a wide range of power supply voltages from 2v to 18v. operation with lower supplies is possible down to 1.2v (two ni-cad batteries). + LT1008 6 v o 2 3 *resistors must have low thermoelectric potential this circuit is also used as the burn-in configuration for the LT1008 with supply voltages increased to 20v v o = 1000v os 100 * 50k* 50k* 7 4 15v 15v 1008 ai02 test circuit for offset voltage and its drift with temperature + LT1008 6 *metal film 1008 ai04 e no 2 10m* 10k 10m* 10m* 10m* 100 3 1008 ai01 guard output inputs v + compensation v 1 8 7 6 5 4 3 2 teflon is a trademark of dupont company microvolt level error voltages can also be generated in the external circuitry. thermocouple effects caused by tem- perature gradients across dissimilar metals at the con- tacts to the input terminals can exceed the inherent drift of the amplifier. air currents over device leads should be minimized, package leads should be short, and the two input leads should be as close together as possible and maintained at the same temperature. noise testing the 0.1hz to 10hz peak-to-peak noise of the LT1008 is measured in the test circuit shown. the frequency re- sponse of this noise tester indicates that the 0.1hz corner is defined by only one zero. the test time to measure 0.1hz to 10hz noise should not exceed 10 seconds, as this time limit acts as an additional zero to eliminate noise contribu- tions from the frequency band below 0.1hz. a noise voltage density test is recommended when mea- suring noise on a large number of units. a 10hz noise voltage density measurement will correlate well with a 0.1hz to 10hz peak-to-peak noise reading since both results are determined by the white noise and the location of the 1/f corner frequency. current noise is measured in the circuit shown and calcu- lated by the following formula where the noise of the source resistors is subtracted. i env m n no = () ? ? w 2 2 12 820 40 100 / reference onlyobsolete package
9 LT1008 applicatio s i for atio wu uu frequency compensation the LT1008 is externally frequency compensated with a single capacitor. the two standard compensation circuits shown earlier are identical to the lm108a/lm308a fre- quency compensation schemes. therefore, the LT1008 operational amplifiers can be inserted directly into lm108a/lm308a sockets, with similar ac and upgraded dc performance. external frequency compensation provides the user with additional flexibility in shaping the frequency response of the amplifier. for example, for a voltage gain of ten and c f = 3pf, a gain bandwidth product of 5mhz and slew rate of 1.2v/ m s can be realized. for closed-loop gains in excess of 200, no external compensation is necessary, and slew rate increases to 4v/ m s. the LT1008 can also be overcom- pensated (i.e., c f > 30pf or c s > 100pf) to improve capaci- tive load handling capability or to narrow noise bandwidth. in many applications, the feedback loop around the ampli- fier has gain (e.g., logarithmic amplifiers); overcompen- sation can stabilize these circuits with a single capacitor. the availability of the compensation terminals permits the use of feedforward frequency compensation to enhance slew rate in low closed-loop gain configurations. the inverter slew rate is increased to 1.4v/ m s. the voltage follower feedforward scheme bypasses the amplifiers gain stages and slews at nearly 10v/ m s. the inputs of the LT1008 are protected with back-to-back diodes. current limiting resistors are not used, because the leakage of these resistors would prevent the realization of picoampere level bias currents at elevated temperatures. in the voltage follower configuration, when the input is driven by a fast, large-signal pulse (>1v), the input protec- tion diodes effectively short the output to the input during slewing, and a current, limited only by the output short- circuit protection, will flow through the diodes. the use of a feedback resistor, as shown in the voltage follower feedforward diagram, is recommended because this resistor keeps the current below the short-circuit limit, resulting in faster recovery and settling of the output. + + LT1008* lt1001 10 100k 2k 100k 110k scope 1 r in = 1m 4.3k 24.3k 0.1 f 1008 ai03 0.1 f *device under test note: all capacitor values are for nonpolarized capacitors only 4.7 f voltage gain: 50,000 2.2 f 22 f + c1 500pf c3 10pf r1 10k r2 10k c2 5pf r3 3k 1 8 1008 ai05 6 v out LT1008 2 input 3 inverter feedforward compensation 0.1hz to 10hz noise test circuit 2v/div 5 m s/div 1008 ai07
10 LT1008 + 1 30pf 330pf 100pf 2k 124k* 5.1k 1k tel. labs type q81 q1a 2n2979 15v output 15v 10k* 15.7k 8 7 6 *1% film resistor low bias current and offset voltage of the LT1008 allow 4.5 decades of voltage input logging 6 2 15v lt1004c 1.2v 3 2 input 3 4 LT1008 q1b 2n2979 + lm107 logarithmic amplifier + LT1008 2 1008 ta04 3 r6 56m 6 output voltage gain 100 1 v + t 8 c1 30pf r5 56m r2 100k r1 100k s1 100k r3 510k r4 510k t s2 100k + 1 1000pf 1.018235v saturated standard cell #101 eppley labs newport, r.i. the typical 30pa bias current of the LT1008 will degrade the standard cell by only 1ppm/year. noise is a fraction of a ppm. unprotected gate mosfet isolates standard cell on power down 15v 15v output 2n3609 r2 r1 1008 ta05 8 7 6 3 2 4 LT1008 + amplifier for bridge transducers saturated standard cell amplifier typical applicatio s u + 1000pf 10k 10k 30pf 8 1008 ai06 6 output *source resistance 15k for stability LT1008 2 input* 3 follower feedforward compensation applicatio s i for atio wu uu 5v/div 5 m s/div 1008 ai07
11 LT1008 typical applicatio s u + 8 2 3 *1% metal film resistor all diodes 1n4148 22k 100pf 1 f 6 22m optional 0.01hz trim 15v 15v 50k 3 6 2 2 v in 0v to 10v 3 7 1 4 LT1008 100k 1.8k 1000pf (polystyrene) 10k* 15v lt1004c 1.2v 10k* 1k 10k 1008 ta08 frequency ouput 0.01hz to 10khz 10k lm329 15v 15v 15v 63.4k* 10k* 750k 10k + + lt311a 15v lm301a 5pf the LT1008 integrator extends low frequency range. total dynamic range is 0.01hz to 10khz (or 120db) with 0.01% linearity. extended range charge pump voltage to frequency converter amplifier for photodiode sensor five decade kelvin-varley divider buffered by the LT1008 + LT1008 2 3 s1 l 6 8 1008 ta06 output c1 100pf v out = 10v/ a r2 5m 1% r1 5m 1% + 1 1000pf 15v 15v 10v 8 7 6 output approximate error due to noise, bias current, common mode rejection. voltage gain of the amplifier is 1/5 of a least significant bit 2 3 100k kelvin-varley divider esi #dp311 00000 ?99999 + 1 4 1008 ta07 LT1008
12 LT1008 typical applicatio s u fast precision inverters + 1 30pf 15v 15v 300pf 1n4148 (4) 8 7 5 4 1 2 3 7 6 output 6 2 3 10k 10k 4 slew rate = 100v/ s settling (10v step) = 5 s to 0.01% offset voltage = 30 v bias current dc = 30pa *1% metal film full power bandwidth = 2mhz slew rate at 50v/ s settling (10v step) = 12 s to 0.01% bias current dc = 30pa offset drift = 0.3 v/ c offset voltage = 30 v *1% metal film LT1008 + 30pf 15v 15v 300pf 10pf 1000pf 10k* 1n4148 2 7 10k input 6 2 3 3 2 10k 4 8 1 1008 ta10 10k 10k* + lt318a 15v 15k input 10k* 10k* 2pf to 8pf 2n4393 2 15v output 7 4 6 + lt318a 15v 15v LT1008 + 1 8 7 8 2 opto-mos* 3 *opto-mos switch type ofm1a theta-j corp 1 4 1000pf filter cut in adjust 15v 15v 10k 100 6 output 10k 2 3 1 f 1k 15v LT1008 1.5m 2k input + #1 lt311a 7 8 5 3 2 1008 ta09 1 4 15v 15v + #2 lt311a precision, fast settling, lowpass filter this circuit is useful where fast signal acquisition and high precision are required, as in electronic scales. the filters time constant is set by the 2k resistor and the 1 m f capacitor until comparator 1 switches. the time constant is then set by the 1.5m resistor and the 1 m f capacitor. comparator 2 provides a quick reset. the circuit settles to a final value three times as fast as a simple 1.5m-1 m f filter with almost no dc error.
13 LT1008 sche atic diagra w w 3 +input 4 v 2 input q13 q16 q15 q18 q19 3.3k s s s q2 q3 q23 q32 q4 q39 q1 q6 22k q9 q10 q5 22k 1.3k 4.2k 3k 1.5k q7 q8 3.3k 16k 20k 3.3k 320 330 40 50k s 1.5k 3k 4.8k 4.3k q11 q12 q21 q20 q29 q24 q25 q27 q43 q22 q28 70 comp1 1 comp2 8 v + 7 output 6 j1 q31 q33 q41 q26 q42 q35 q17 q34 q40 q14 q30 3k 60 q38 q37
14 LT1008 u package descriptio h8(to-5) 0.200 pcd 1197 0.050 (1.270) max 0.016 ?0.021** (0.406 ?0.533) 0.010 ?0.045* (0.254 ?1.143) seating plane 0.040 (1.016) max 0.165 ?0.185 (4.191 ?4.699) gauge plane reference plane 0.500 ?0.750 (12.700 ?19.050) 0.305 ?0.335 (7.747 ?8.509) 0.335 ?0.370 (8.509 ?9.398) dia lead diameter is uncontrolled between the reference plane and 0.045" below the reference plane for solder dip lead finish, lead diameter is 0.016 ?0.024 (0.406 ?0.610) * ** 0.200 (5.080) typ 0.027 ?0.045 (0.686 ?1.143) 0.028 ?0.034 (0.711 ?0.864) 0.110 ?0.160 (2.794 ?4.064) insulating standoff 45 typ pin 1 obsolete packages j8 1298 0.014 ?0.026 (0.360 ?0.660) 0.200 (5.080) max 0.015 ?0.060 (0.381 ?1.524) 0.125 3.175 min 0.100 (2.54) bsc 0.300 bsc (0.762 bsc) 0.008 ?0.018 (0.203 ?0.457) 0 ?15 0.005 (0.127) min 0.405 (10.287) max 0.220 ?0.310 (5.588 ?7.874) 12 3 4 87 65 0.025 (0.635) rad typ 0.045 ?0.068 (1.143 ?1.727) full lead option 0.023 ?0.045 (0.584 ?1.143) half lead option corner leads option (4 plcs) 0.045 ?0.065 (1.143 ?1.651) note: lead dimensions apply to solder dip/plate or tin plate leads h package 8-lead to-5 metal can (.200 inch pcd) (reference ltc dwg # 05-08-1320) j8 package 8-lead cerdip (narrow .300 inch, hermetic) (reference ltc dwg # 05-08-1110)
15 LT1008 information furnished by linear technology corporation is believed to be accurate and reliable. however, no responsibility is assumed for its use. linear technology corporation makes no represen- tation that the interconnection of its circuits as described herein will not infringe on existing patent rights. u package descriptio n8 1098 0.100 (2.54) bsc 0.065 (1.651) typ 0.045 ?0.065 (1.143 ?1.651) 0.130 0.005 (3.302 0.127) 0.020 (0.508) min 0.018 0.003 (0.457 0.076) 0.125 (3.175) min 12 3 4 87 6 5 0.255 0.015* (6.477 0.381) 0.400* (10.160) max 0.009 ?0.015 (0.229 ?0.381) 0.300 ?0.325 (7.620 ?8.255) 0.325 +0.035 0.015 +0.889 0.381 8.255 () *these dimensions do not include mold flash or protrusions. mold flash or protrusions shall not exceed 0.010 inch (0.254mm) 0.016 ?0.050 (0.406 ?1.270) 0.010 ?0.020 (0.254 ?0.508) 45 0 ?8 typ 0.008 ?0.010 (0.203 ?0.254) so8 1298 0.053 ?0.069 (1.346 ?1.752) 0.014 ?0.019 (0.355 ?0.483) typ 0.004 ?0.010 (0.101 ?0.254) 0.050 (1.270) bsc 1 2 3 4 0.150 ?0.157** (3.810 ?3.988) 8 7 6 5 0.189 ?0.197* (4.801 ?5.004) 0.228 ?0.244 (5.791 ?6.197) dimension does not include mold flash. mold flash shall not exceed 0.006" (0.152mm) per side dimension does not include interlead flash. interlead flash shall not exceed 0.010" (0.254mm) per side * ** n8 package 8-lead pdip (narrow .300 inch) (reference ltc dwg # 05-08-1510) s8 package 8-lead plastic small outline (narrow .150 inch) (reference ltc dwg # 05-08-1610)
16 LT1008 part number description comments lt1012 picoamp input current, microvolt offset, low noise op amp internally compensated LT1008 lt1112 dual low power, precision, picoamp input op amp dual lt1012 lt1880 sot-23, rail-to-rail output, picoamp input current precision op amp single sot-23 version of lt1884 lt1881/lt1882 dual and quad rail-to-rail output, picoamp input precision op amps dual/quad c load stable lt1884/lt1885 dual and quad rail-to-rail output, picoamp input precision op amps dual/quad faster lt1881/lt1882 ? linear technology corporation 1991 1008fa lt/tp 0701 1.5k rev a ? printed in the usa related parts linear technology corporation 1630 mccarthy blvd., milpitas, ca 95035-7417 (408) 432-1900 l fax: (408) 434-0507 l www.linear.com u typical applicatio ammeter measures currents from 100pa to 100 m a with- out the use of expensive high value resistors. accuracy at 100 m a is limited by the offset voltage between q1 and q2 and at 100pa by the inverting bias current of the LT1008. ammeter with six decade range + 15v 0.01 f 15v 7 6 2 current input 3 10k 4 8 1 33k range 1na 10na LT1008 q4 q2 pin 13 ca3146 q1 q3 100 a meter 15v 549 100na 549 lt1004c-1.2 100pa 549 1.2k r1 2k 10k 1 a 549 q1 to q4: rca ca3146 transistor array calibration: adjust r1 for full scale deflection with 1 a input current 10 a 549 100 a 549 1008 ta11

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