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November 2006 rev 0.3 Low Voltage Zero Delay Buffer
Features
Fully Integrated PLL Up to 200MHz I/O Frequency LVCMOS Outputs Outputs Disable in High Impedance LVCMOS Reference Clock Options LQFP and TQFP Packaging 50pS Cycle-Cycle Jitter 150pS Output Skews The PCS5I961 is The offered with
PCS5I961C
two offers
different an
input
configurations. reference clock.
PCS5I961C
LVCMOS
reference clock while the PCS5I961P offers an LVPECL
When pulled high the OE pin will force all of the outputs (except QFB) into a high impedance state. Because the OE pin does not affect the QFB output, down stream clocks can be disabled without the internal PLL losing lock. The PCS5I961C is fully 2.5V or 3.3V compatible and requires no external loop filter components. All control inputs accept LVCMOS compatible levels and the outputs provide low impedance LVCMOS outputs capable of driving terminated 50 transmission lines. For series terminated lines the PCS5I961C can drive two lines per output giving the device an effective fanout of 1:36. The device is packaged in a 32 lead LQFP and TQFP Packages.
Functional Description
The PCS5I961C is a 2.5V or 3.3V compatible, 1:18 PLL based zero delay buffer. With output frequencies of up to 200MHz, output skews of 150pS the device meets the needs of the most demanding clock tree applications.
Block Diagram
Q0 CCLK 50K FB_IN 50K F_RANGE 50K Q14 Q15 Q16 OE 50K
Figure 1. PCS5I961C Logic Diagram
PLL Ref 100-200 MHz FB 50-100 MHz
Q1 0 1 Q2 Q3
QFB
PulseCore Semiconductor Corporation 1715 S. Bascom Ave Suite 200, Campbell, CA 95008 * Tel: 408-879-9077 * Fax: 408-879-9018 www.pulsecoresemi.com
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November 2006 rev 0.3
Pin Configuration
GND VCC Q10 Q11 Q6 Q7 Q8 Q9
PCS5I961C
24 23 22 21 20 19 18 17 Q5 Q4 Q3 GND Q2 Q1 Q0 VCC 25 26 27 28 29 30 31 32 1 2 3 4 5 6 7 8 16 15 14 VCC Q12 Q13 Q14 GND Q15 Q16 QFB
PCS5I961C
13 12 11 10 9
FB_IN
GND
NC
F_RANGE
CCLK
c
Figure 2. PCS5I961C 32-Lead Package Pinout (Top View)
Table 1: Pin Configuration Pin #
2 7 4
Pin Name
CCLK FB_IN F_RANGE OE Q0 - Q16 QFB GND
I/O
Input Input Input Input Output Output Supply
VCCA
Type
LVCMOS LVCMOS LVCMOS LVCMOS LVCMOS LVCMOS Ground
VCC
OE
Function
PLL reference clock signal PLL feedback signal input, connect to a QFB output PLL frequency range select Output enable/disable Clock outputs PLL feedback signal output, connect to a FB_IN Negative power supply PLL positive power supply (analog power supply). The PCS5I961C requires an external RC filter for the analog power supply pin VCCA. Please see applications section for details. Positive power supply for I/O and core Not connected
6
31,30,29,27,26,25,23,22,21, 19,18,17,15,14,13,11,10 9 1,12,20,28
5
VCCA
Supply
VCC
8,16,24,32 3
VCC NC
Supply
VCC
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Table 2: FUNCTION TABLE
Control F_RANGE OE Default 0 0 0 PLL high frequency range. PCS5I961C input reference and output clock frequency range is 100 - 200MHz Outputs enabled
PCS5I961C
1 PLL low frequency range. PCS5I961C input reference and output clock frequency range is 50 - 100MHz Outputs disabled (high-impedance state)
Table 3: ABSOLUTE MAXIMUM RATINGS1
Symbol VCC VIN VOUT IIN IOUT TS Supply Voltage DC Input Voltage DC Output Voltage DC Input Current DC Output Current Storage Temperature Range -40 Parameter Min -0.3 -0.3 -0.3 Max 3.6 VCC + 0.3 VCC + 0.3 20 50 125 Unit V V V mA mA C
Note: 1 These are stress ratings only and are not implied for functional use. Exposure to absolute maximum ratings for prolonged periods of time may affect device reliability.
Table 4: DC CHARACTERISTICS (VCC = 3.3V 5%, TA = -40C to +85C)
Symbol VIH VIL VOH VOL ZOUT IIN CIN CPD ICCA ICC VTT Characteristic Input HIGH Voltage Input LOW Voltage Output HIGH Voltage Output LOW Voltage Output Impedance Input Current Input Capacitance Power Dissipation Capacitance Maximum PLL Supply Current Maximum Quiescent Supply Current Output Termination Voltage 4.0 8.0 2.0 VCC/2 10 5.0 TBD 14 Min 2.0 -0.3 2.4 0.55 20 120 Typ Max VCC + 0.3 0.8 Unit V V V V A pF pF mA mA V Per Output VCCA Pin All VCC Pins Condition LVCMOS LVCMOS IOH = -20mA1 IOL = 20mA1
Note: 1. The PCS5I961C is capable of driving 50 transmission lines on the incident edge. Each output drives one 50 parallel terminated transmission line to a termination voltage of VTT. Alternatively, the device drives up two 50 series terminated transmission lines.
Low Voltage Zero Delay Buffer
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Table 5: AC CHARACTERISTICS (VCC = 3.3V 5%, TA = 40C to +85C)1
Symbol fref fmax frefDC tr, tf t() tsk(O) DCO tr, tf tPLZ,HZ tPZL,LZ tJIT(CC) tJIT(PER) tJIT() tlock Characteristic Input Frequency Maximum Output Frequency F_RANGE = 0 F_RANGE = 1 F_RANGE = 0 F_RANGE = 1 Min 100 50 100 50 25 Typ Max 200 100 200 100 75 3.0 -80 90 F_RANGE = 0 F_RANGE = 1 42 45 0.1 50 50 120 150 55 55 1.0 10 10 RMS (1) RMS (1)
3
PCS5I961C
Unit MHz MHz % nS pS pS % nS nS nS pS pS nS mS 0.55 to 2.4V 0.8 to 2.0V PLL locked Condition
Reference Input Duty Cycle TCLK Input Rise/Fall Time Propagation Delay (static phase offset) Output-to-Output Skew2 Output Duty Cycle Output Rise/Fall Time Output Disable Time Output Enable Time Cycle-to-Cycle Jitter Period Jitter CCLK to FB_IN
15 7.0 10 15 10
I/O Phase Jitter RMS (1) Maximum PLL Lock Time
Note: 1. AC characteristics apply for parallel output termination of 50 to VTT. 2. See applications section for part-to-part skew calculation 3. See applications section for calculation for other confidence factors than 1
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Table 6: DC CHARACTERISTICS (VCC = 2.5V 5%, TA = -40 to 85C)
Symbol VIH VIL VOH VOL ZOUT IIN CIN CPD ICCA ICC VTT Characteristic Input HIGH Voltage Input LOW Voltage Output HIGH Voltage Output LOW Voltage Output Impedance Input Current Input Capacitance Power Dissipation Capacitance Maximum PLL Supply Current Maximum Quiescent Supply Current Output Termination Voltage 4.0 8.0 2.0 VCC /2 10 5.0 TBD 18 Min 1.7 -0.3 1.8 0.6 26 120 Typ Max VCC + 0.3 0.7 Unit V V V V mA pF pF mA mA V
PCS5I961C
Condition LVCMOS LVCMOS IOH = -15mA1 IOL = 15mA1
Per Output VCCA Pin All VCC Pins
Note: 1.The PCS5I961C is capable of driving 50 transmission lines on the incident edge. Each output drives one 50 parallel terminated transmission line to a termination voltage of VTT. Alternatively, the device drives up two 50 series terminated transmission lines.
Table 7: AC CHARACTERISTICS (VCC = 2.5V 5%, TA = 40C to +85C)1
Symbol fref fmax frefDC tr, tf t() tsk(O) DCO tr, tf tPLZ,HZ tPZL,LZ tJIT(CC) tJIT(PER) tJIT() tlock Characteristic Input Frequency Maximum Output Frequency F_RANGE = 0 F_RANGE = 1 F_RANGE = 0 F_RANGE = 1 Min 100 50 100 50 25 Typ Max 200 100 200 100 75 3.0 -80 90 F_RANGE = 0 F_RANGE = 1 40 45 0.1 50 50 120 150 60 55 1.0 10 10 RMS (1) RMS (1)
3
Unit MHz MHz % nS pS pS % nS nS nS pS pS nS mS
Condition
Reference Input Duty Cycle TCLK Input Rise/Fall Time Propagation Delay (static phase offset) Output-to-Output Skew Output Duty Cycle Output Rise/Fall Time Output Disable Time Output Enable Time Cycle-to-Cycle Jitter Period Jitter
2
0.7 to 1.7V PLL locked
CCLK to FB_IN
0.6 to 1.8V
15 7.0 10 15 10
I/O Phase Jitter RMS (1) Maximum PLL Lock Time
Note: 1 AC characteristics apply for parallel output termination of 50 to VTT. 2 See applications section for part-to-part skew calculation 3 See applications section for calculation for other confidence factors than 1
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APPLICATIONS INFORMATION
Power Supply Filtering The PCS5I961C is a mixed analog/digital product and as such it exhibits some sensitivity that would not necessarily be seen on a fully digital product. Analog circuitry is naturally susceptible to random noise, especially if this noise is seen on the power supply pins. The PCS5I961C provides separate power supplies for the output buffers (VCC) and the phase-locked loop (VCCA) of the device. The purpose of this design technique is to isolate the high switching noise digital outputs from the relatively sensitive internal analog phase-locked loop. In a controlled environment such as an evaluation board this level of isolation is sufficient. However, in a digital system environment where it is more difficult to minimize noise on the power supplies a second level of isolation may be required. The simplest form of isolation is a power supply filter on the VCCA pin for the PCS5I961C. Figure 3. illustrates a typical power supply filter scheme. The PCS5I961C is most susceptible to noise with spectral content in the 10KHz to 10MHz range. Therefore the filter should be designed to target this range. The key parameter that needs to be met in the final filter design is the DC voltage drop that will be seen between the VCC supply and the VCCA pin of the PCS5I961C. From the data sheet the ICCA current (the current sourced through the VCCA pin) is typically 2mA (5mA maximum), assuming that a minimum of 2.375V (VCC = 3.3V or VCC = 2.5V) must be maintained on the VCCA pin. The resistor RF shown in Figure 3. must have a resistance of 270 (VCC = 3.3V) or 5 to 15 (VCC = 2.5V) to meet the voltage drop criteria. The RC filter pictured will provide a broadband filter with approximately 100:1 attenuation for noise whose spectral content is above 20KHz. As the noise frequency crosses the series resonant point of an individual capacitor it's overall impedance begins to look inductive and thus increases with increasing frequency. The parallel capacitor combination shown ensures that a low impedance path to ground exists for frequencies well above the bandwidth of the PLL.
RF = 270 for VCC = 3.3V RF = 5-15 for VCC = 2.5V RF VCC 22 F 10 nF VCCA
PCS5I961C
may be applications in which overall performance is being degraded due to system power supply noise. The power supply filter schemes discussed in this section should be adequate to eliminate power supply noise related problems in most designs. Driving Transmission Lines The PCS5I961C clock driver was designed to drive high speed signals in a terminated transmission line environment. To provide the optimum flexibility to the user the output drivers were designed to exhibit the lowest impedance possible. With an output impedance of less than 15 the drivers can drive either parallel or series terminated transmission lines. In most high performance clock networks point-to-point distribution of signals is the method of choice. In a point-to-point scheme either series terminated or parallel terminated transmission lines can be used. The parallel technique terminates the signal at the end of the line with a 50 resistance to VCC/2. This technique draws a fairly high level of DC current and thus only a single terminated line can be driven by each output of the PCS5I961C clock driver. For the series terminated case however there is no DC current draw, thus the outputs can drive multiple series terminated lines. Figure 4. illustrates an output driving a single series terminated line vs two series terminated lines in parallel. When taken to its extreme the fanout of the PCS5I961C clock driver is effectively doubled due to its capability to drive multiple lines.
PCS5I961C OUTPUT BUFFER IN 14 RS=36 Z0=50 OUTA
PCS5I961C OUTPUT BUFFER IN 14
RS=36
Z0=50 OUTB0
RS=36
Z0=50 OUTB1
Figure 4. Single versus Dual Transmission Lines The waveform plots of Figure 5. show the simulation results of an output driving a single line vs two lines. In both cases the drive capability of the PCS5I961C output buffer is more than sufficient to drive 50 transmission lines on the incident edge. Note from the delay measurements in the simulations a delta of only 43pS exists between the two differently loaded outputs. This suggests that the dual line driving need not be used exclusively to maintain the tight output-to-output skew of the PCS5I961C. The output waveform in Figure 5. shows a step in the waveform, this step is caused by the impedance mismatch seen looking into the driver. The parallel combination of the 36 series resistor plus the
VCC 33...100 nF
Figure 3. Power Supply Filter Although the PCS5I961C has several design features to minimize the susceptibility to power supply noise (isolated power and grounds and fully differential PLL) there still
Low Voltage Zero Delay Buffer
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output impedance does not match the parallel combination of the line impedances. The voltage wave launched down the two lines will equal: VL = VS ( Zo / (Rs + Ro +Zo)) Zo = 50 || 50 Rs = 36 || 36 Ro = 14 VL = 3.0 (25 / (18 + 14 + 25) = 3.0 (25 / 57) = 1.31V At the load end the voltage will double, due to the near unity reflection coefficient, to 2.62V. It will then increment towards the quiescent 3.0V in steps separated by one round trip delay (in this case 4.0nS).
3.0 OutA tD = 3.8956 OutB tD = 3.9386
PCS5I961C
Using the PCS5I961C in zero-delay applications Nested clock trees are typical applications for the PCS5I961C. Designs using the PCS5I961C as LVCMOS PLL fanout buffer with zero insertion delay will show significantly lower clock skew than clock distributions developed from CMOS fanout buffers. The external feedback option of the PCS5I961C clock driver allows for its use as a zero delay buffer. By using the QFB output as a feedback to the PLL the propagation delay through the device is virtually eliminated. The PLL aligns the feedback clock output edge with the clock input reference edge resulting a near zero delay through the device. The maximum insertion delay of the device in zero-delay applications is measured between the reference clock input and any output. This effective delay consists of the static phase offset, I/O jitter (phase or long-term jitter), feedback path delay and the output-to-output skew error relative to the feedback output. Calculation of part-to-part skew
2.5 VOLTAGE (V)
2.0 In 1.5
1.0
The PCS5I961C zero delay buffer supports applications where critical clock signal timing can be maintained across several devices. If the reference clock inputs of two or more PCS5I961C are connected together, the maximum overall timing uncertainty from the common CCLK input to any output is: tSK(PP) = t() + tSK(O) + tPD, LINE(FB) + tJIT() CF This maximum timing uncertainty consist of 4 components: static phase offset, output skew, feedback board trace delay and I/O (phase) jitter:
PCLKCommon -t(O) QFBDevice 1 tJIT(O) Any QDevice 1 +tSK(O) +t(O QFBDevice 2 tJIT(O) Any QDevice 2 Max. skew tSK(PP) tPD,LINE (FB)
0.5
0 2 4 6 8 10 12 14
TIME (nS)
Figure 5. Single versus Dual Waveforms Since this step is well above the threshold region it will not cause any false clock triggering, however designers may be uncomfortable with unwanted reflections on the line. To better match the impedances when driving multiple lines the situation in Figure 6. should be used. In this case the series terminating resistors are reduced such that when the parallel combination is added to the output buffer impedance the line impedance is perfectly matched.
PCS5I961C OUTPUT BUFFER IN 14 RS=22 RS=22 Z0=50
Z0=50
14 + 22 22 = 50 50 25 = 25 Figure 6. Optimized Dual Line Termination
+tSK(O)
Figure 7. PCS5I961C max. device-to-device skew
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Due to the statistical nature of I/O jitter a rms value (1) is specified. I/O jitter numbers for other confidence factors (CF) can be derived from Table 8.
PCS5I961C
frequency, supply voltage, output loading, ambient temperature, vertical convection and thermal conductivity of package and board. This section describes the impact of these parameters on the junction temperature and gives a guideline to estimate the PCS5I961C die junction temperature and the associated device reliability. Table 9: Die junction temperature and MTBF Junction temperature (C) 100 110 120 130 MTBF (Years) 20.4 9.1 4.2 2.0
Table 8: Confidence Factor CF CF 1 2 3 4 5 6 Probability of clock edge within the distribution 0.68268948 0.95449988 0.99730007 0.99993663 0.99999943 0.99999999
The feedback trace delay is determined by the board layout and can be used to fine-tune the effective delay through each device. In the following example calculation a I/O jitter confidence factor of 99.7% ( 3 ) is assumed, resulting in a worst case timing uncertainty from input to any output of -275 pS to 315 pS relative to CCLK: tSK(PP) = [-80pS...120pS] + [-150pS...150pS] + [(15pS* -3)...(15pS* 3)] + tPD, LINE(FB) tSK(PP) = [-275pS...315pS] + tPD, LINE(FB) Due to the frequency dependence of the I/O jitter, Figure 8. "Max. I/O Jitter versus frequency" can be used for a more precise timing performance analysis.
18 tjit(O)[ps] RMS 16 14 12 10 8 6 4 2 0 50 70 90 110 130 170 190 150 Clock frequency [MHz] VCC=3.3V VCC=2.5V VCC=3.3V VCC=2.5V F_RANGE=1 F_RANGE=0 TA = 85C
Increased power consumption will increase the die junction temperature and impact the device reliability (MTBF). According to the system-defined tolerable MTBF, the die junction temperature of the PCS5I961C needs to be controlled and the thermal impedance of the board/package should be optimized. The power dissipated in the PCS5I961C is represented in equation 1. Where ICCQ is the static current consumption of the PCS5I961C, CPD is the power dissipation capacitance per output, (M)CL represents the external capacitive output load, N is the number of active outputs (N is always 27 in case of the PCS5I961C). The PCS5I961C supports driving transmission lines to maintain high signal integrity and tight timing parameters. Any transmission line will hide the lumped capacitive load at the end of the board trace, therefore, CL is zero for controlled transmission line systems and can be eliminated from equation 1. Using parallel termination output termination results in equation 2 for power dissipation. In equation 2, P stands for the number of outputs with a parallel or thevenin termination, VOL, IOL, VOH and IOH are a function of the output termination technique and DCQ is the clock signal duty cycle. If transmission lines are used CL is zero in equation 2 and can be eliminated. In general, the use of controlled transmission line techniques eliminates the impact of the lumped capacitive loads at the end lines and greatly reduces the power dissipation of the device. Equation 3 describes the die junction temperature TJ as a function of the power consumption.
Figure 8. Max. I/O Jitter versus frequency Power Consumption of the PCS5I961C and Thermal Management The PCS5I961C AC specification is guaranteed for the entire operating frequency range up to 200MHz. The PCS5I961C power consumption and the associated longterm reliability may decrease the maximum frequency limit, depending on operating conditions such as clock
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PCS5I961C
PTOT = I CCQ + VCC f CLOCK N C PD + C L VCC Equation 1 M PTOT = VCC I CCQ + VCC f CLOCK N C PD + C L + DC Q I OH (VCC - VOH ) + (1 - DC Q ) I OL VOL Equation 2 M P TJ = T A + PTOT Rthja Equation 3
[
]
f CLOCKMAX =
C PD
1 2 N VCC
T - TA JMAX - (I CCQ VCC ) Rthja
Equation 4
Where Rthja is the thermal impedance of the package (junction to ambient) and TA is the ambient temperature. According to Table 9, the junction temperature can be used to estimate the long-term device reliability. Further, combining equation 1 and equation 2 results in a maximum operating frequency for the PCS5I961C in a series terminated transmission line system. Table 10: Thermal package impedance of the 32LQFP Convection, LFPM Rthja (1P2S board), C/W Still air 80 100 lfpm 70 200 lfpm 61 300 lfpm 57 400 lfpm 56 500 lfpm 55 TJ,MAX should be selected according to the MTBF system requirements and Table 9. Rthja can be derived from
Table 10. The Rthja represent data based on 1S2P boards, using 2S2P boards will result in a lower thermal impedance than indicated below. If the calculated maximum frequency is below 200MHz, it becomes the upper clock speed limit for the given application conditions. The following two derating charts describe the safe frequency operation range for the PCS5I961C. The charts were calculated for a maximum tolerable die junction temperature of 110C, corresponding to an estimated MTBF of 9.1 years, a supply voltage of 3.3V and series terminated transmission line or capacitive loading. Depending on a given set of these operating conditions and the available device convection a decision on the maximum operating frequency can be made. There are no operating frequency limitations if a 2.5V power supply or the system specifications allow for a MTBF of 4 years (corresponding to a max. junction temperature of 120C.
200 Operating frequency (MHz) 190 160 140 120 100 80 60 40 20 0 500 400
fMAX (AC) Operating frequency (MHz)
200 190 160 140 120 100 80 60 40 20 0
fMAX (AC)
TA = 85 C
TA = 75C TA = 85C
Safe operation
Safe operation
200 300 Convection Ifpm
100
0
500
400
200 300 Convection Ifpm
100
0
Figure 9. Maximum PCS5I961C frequency, VCC = 3.3V, MTBF 9.1 years, driving series terminated transmission lines
Figure 10. Maximum PCS5I961C frequency, VCC = 3.3V, MTBF 9.1 years,4pF load per line
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Pulse Generator Z=50 Z0=50 Z0=50
PCS5I961C
RT=50
RT=50
VTT
VTT
Figure 11. TCLK PCS5I961C AC test reference for VCC = 3.3V and VCC = 2.5V
VCC VCC /2 GND VCC VCC /2 tSK(O) GND FB_IN t(O) CCLK VCC VCC /2 GND VCC VCC /2 GND
The pin-to-pin skew is defined as the worst case difference in propagation delay between any similar delay path within a single device
Figure 13. Propagation delay (tPD, static phase offset) test reference
Figure 12. Output-to-Output Skew tSK(O)
VCC VCC /2 GND tP T0 DC= (tP /T0 100%) FB_IN TJIT(O) =T0-T1 mean CCLK
The time from the PLL controlled edge to the non-controlled edge, divided by the time between PLL controlled edges, expressed as a percentage.
The deviation in t0 for a controlled edge with respect to a t0 mean in a random sample of cycles
Figure 15.I/O Jitter
Figure 14. Output Duty Cycle (DC)
TN TN+1
T0
TJIT(PER) =TN-1/f0
TJIT(CC) =TN-TN+1
The deviation in cycle time of a signal with respect to the ideal period over a random sample of cycles
The variation in cycle time of a signal between adjacent cycles, over a random sample of adjacent cycle pairs
Figure 17. Period Jitter
Figure 16. Cycle-to-cycle Jitter
VCC = 3.3V 2.4 0.55 tF tR VCC = 2.5V 1.8V 0.6V
Figure 18. Output Transition Time Test Reference
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Package Diagram 32-lead TQFP
PCS5I961C
SECTION A-A
Dimensions Symbol
A A1 A2 D D1 E E1 L L1 T T1 b b1 R0 a e
Inches Min Max
.... 0.0020 0.0374 0.3465 0.2717 0.3465 0.2717 0.0177 0.0035 0.0038 0.0118 0.0118 0.0031 0 0.0472 0.0059 0.0413 0.3622 0.2795 0.3622 0.2795 0.0295 0.0079 0.0062 0.0177 0.0157 0.0079 7
Millimeters Min Max
... 0.05 0.95 8.8 6.9 8.8 6.9 0.45 0.09 0.097 0.30 0.30 0.08 0 0.8 BASE 1.2 0.15 1.05 9.2 7.1 9.2 7.1 0.75 0.2 0.157 0.45 0.40 0.2 7
0.03937 REF
1.00 REF
0.031 BASE
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PCS5I961C
32-lead LQFP
SECTION A-A
Dimensions Symbol
A A1 A2 D D1 E E1 L L1 T T1 b b1 R0 e a
Inches Min Max
.... 0.0020 0.0531 0.3465 0.2717 0.3465 0.2717 0.0177 0.0035 0.0038 0.0118 0.0118 0.0031 0 0.0630 0.0059 0.0571 0.3622 0.2795 0.3622 0.2795 0.0295 0.0079 0.0062 0.0177 0.0157 0.0079 7
Millimeters Min Max
... 0.05 1.35 8.8 6.9 8.8 6.9 0.45 0.09 0.097 0.30 0.30 0.08 0 1.6 0.15 1.45 9.2 7.1 9.2 7.1 0.75 0.2 0.157 0.45 0.40 0.20 7
0.03937 REF
1.00 REF
0.031 BASE
0.8 BASE
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Ordering Information Part Number
PCS5I961CG-32-ET PCS5I961CG-32-LT
PCS5I961C
Marking
PCS5I961CG PCS5I961CG
Package Type
32 pin TQFP, Green 32 pin LQFP - Tape and Reel, Green
Temperature
Industrial Industrial
Device Ordering Information
PCS
5I961C
G-32-LT
R = Tape & Reel, T = Tube or Tray O = SOT S = SOIC T = TSSOP A = SSOP V = TVSOP B = BGA Q = QFN DEVICE PIN COUNT U = MSOP E = TQFP L = LQFP U = MSOP P = PDIP D = QSOP X = SC-70
G = GREEN PACKAGE, LEAD FREE, and RoHS
PART NUMBER X= Automotive I= Industrial P or n/c = Commercial (-40C to +125C) (-40C to +85C) (0C to +70C) 1 = Reserved 2 = Non PLL based 3 = EMI Reduction 4 = DDR support products 5 = STD Zero Delay Buffer 6 = Power Management 7 = Power Management 8 = Power Management 9 = Hi Performance 0 = Reserved
PulseCore Semiconductor Mixed Signal Product
Licensed under US patent #5,488,627, #6,646,463 and #5,631,920.
Low Voltage Zero Delay Buffer
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PCS5I961C
PulseCore Semiconductor Corporation 1715 S. Bascom Ave Suite 200 Campbell, CA 95008 Tel: 408-879-9077 Fax: 408-879-9018 www.pulsecoresemi.com
Copyright (c) PulseCore Semiconductor All Rights Reserved Preliminary Information Part Number: PCS5I961C Document Version: 0.3
Note: This product utilizes US Patent # 6,646,463 Impedance Emulator Patent issued to PulseCore Semiconductor, dated 11-11-2003
(c) Copyright 2006 PulseCore Semiconductor Corporation. All rights reserved. Our logo and name are trademarks or registered trademarks of PulseCore Semiconductor. All other brand and product names may be the trademarks of their respective companies. PulseCore reserves the right to make changes to this document and its products at any time without notice. PulseCore assumes no responsibility for any errors that may appear in this document. The data contained herein represents PulseCore's best data and/or estimates at the time of issuance. PulseCore reserves the right to change or correct this data at any time, without notice. If the product described herein is under development, significant changes to these specifications are possible. The information in this product data sheet is intended to be general descriptive information for potential customers and users, and is not intended to operate as, or provide, any guarantee or warrantee to any user or customer. PulseCore does not assume any responsibility or liability arising out of the application or use of any product described herein, and disclaims any express or implied warranties related to the sale and/or use of PulseCore products including liability or warranties related to fitness for a particular purpose, merchantability, or infringement of any intellectual property rights, except as express agreed to in PulseCore's Terms and Conditions of Sale (which are available from PulseCore). All sales of PulseCore products are made exclusively according to PulseCore's Terms and Conditions of Sale. The purchase of products from PulseCore does not convey a license under any patent rights, copyrights; mask works rights, trademarks, or any other intellectual property rights of PulseCore or third parties. PulseCore does not authorize its products for use as critical components in life-supporting systems where a malfunction or failure may reasonably be expected to result in significant injury to the user, and the inclusion of PulseCore products in such life-supporting systems implies that the manufacturer assumes all risk of such use and agrees to indemnify PulseCore against all claims arising from such use.
Low Voltage Zero Delay Buffer
Notice: The information in this document is subject to change without notice.
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