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| TS4972 1.2W Audio Power Amplifier with Standby Mode Active High Operating from VCC = 2.5V to 5.5V Rail-to-rail output 1.2W output power @ Vcc=5V, THD=1%, F=1kHz, with 8 load Ultra low consumption in standby mode (10nA) 75dB PSRR @ 217Hz from 2.5 to 5V Low pop & click Ultra low distortion (0.05%) Unity gain stable Flip-chip package 8 x 300m bumps Pin Connections (top view) TS4972JT - FLIP CHIP 7 Vin + 6 Vcc 5 Stdby 8 Vout1 Vout2 4 Vin Gnd Bypass Description The TS4972 is an Audio Power Amplifier capable of delivering 1.6W of continuous RMS ouput power into a 4 load @ 5V. This Audio Amplifier is exhibiting 0.1% distortion level (THD) from a 5V supply for a Pout = 250mW RMS. An external standby mode control reduces the supply current to less than 10nA. An internal shutdown protection is provided. The TS4972 has been designed for high quality audio applications such as mobile phones and to minimize the number of external components. The unity-gain stable amplifier can be configured by external gain setting resistors. VCC 3 5 Bypass Standby Audio Input Cin 7 Vin+ 1 2 3 TYPICAL APPLICATION SCHEMATIC Cfeed Rfeed VCC 6 VCC Rin 1 VinVout 1 + RL 8 Ohms AV = -1 + Bias GND Cb 2 Vout 2 4 8 Cs Applications Mobile phones (cellular / cordless) PDAs Laptop/notebook computers Portable audio devices Rstb TS4972 Order Codes Part Number TS4972IJT TS4972EIJT1 Temperature Range -40, +85C Package Flip-Chip Packing Tape & Reel Marking 4972 1) Lead free Flip-Chip part number October 2004 Revision 2 1/30 TS4972 1 Absolute Maximum Ratings Absolute Maximum Ratings Table 1: Key parameters and their absolute maximum ratings Symbol VCC Vi Toper Tstg Tj Rthja Pd Supply voltage 2 1 Parameter Value 6 GND to VCC -40 to + 85 -65 to +150 150 200 Internally Limited4 2 200 Class A 250 Unit V V C C C C/W kV V C Input Voltage Operating Free Air Temperature Range Storage Temperature Maximum Junction Temperature Thermal Resistance Junction to Ambient 3 Power Dissipation ESD Human Body Model ESD Machine Model Latch-up Latch-up Immunity Lead Temperature (soldering, 10sec) 1) All voltages values are measured with respect to the ground pin. 2) The magnitude of input signal must never exceed VCC + 0.3V / GND - 0.3V 3) Device is protected in case of over temperature by a thermal shutdown active @ 150C. 4) Exceeding the power derating curves during a long period, involves abnormal operating condition. Table 2: Operating Conditions Symbol VCC VICM VSTB RL Rthja Parameter Supply Voltage Common Mode Input Voltage Range Standby Voltage Input : Device ON Device OFF Load Resistor Thermal Resistance Junction to Ambient 1 Value 2.5 to 5.5 GND to VCC - 1.2V GND VSTB 0.5V VCC - 0.5V VSTB VCC 4 - 32 90 Unit V V V C/W 1) With Heat Sink Surface = 125mm2 2/30 Electrical Characteristics 2 Electrical Characteristics TS4972 Table 3: VCC = +5V, GND = 0V, Tamb = 25C (unless otherwise specified) Symbol ICC ISTANDBY Voo Po THD + N PSRR M GM GBP Parameter Supply Current No input signal, no load Standby Current 1 No input signal, Vstdby = Vcc, RL = 8 Output Offset Voltage No input signal, RL = 8 Output Power THD = 1% Max, f = 1kHz, RL = 8 Total Harmonic Distortion + Noise Po = 250mW rms, Gv = 2, 20Hz < f < 20kHz, RL = 8 Power Supply Rejection Ratio2 f = 217Hz, RL = 8, RFeed = 22K, Vripple = 200mV rms Phase Margin at Unity Gain RL = 8, CL = 500pF Gain Margin RL = 8, CL = 500pF Gain Bandwidth Product RL = 8 Min. Typ. 6 10 5 1.2 0.1 75 70 20 2 Max. 8 1000 20 Unit mA nA mV W % dB Degrees dB MHz 1) Standby mode is actived when Vstdby is tied to Vcc 2) Dynamic measurements - 20*log(rms(Vout)/rms(Vripple)). Vripple is an added sinus signal to Vcc @ f = 217Hz 3/30 TS4972 Electrical Characteristics Table 4: VCC = +3.3V, GND = 0V, Tamb = 25C (unless otherwise specified)3) Symbol ICC ISTANDBY Voo Po THD + N PSRR M GM GBP Parameter Supply Current No input signal, no load Standby Current 1 No input signal, Vstdby = Vcc, RL = 8 Output Offset Voltage No input signal, RL = 8 Output Power THD = 1% Max, f = 1kHz, RL = 8 Total Harmonic Distortion + Noise Po = 250mW rms, Gv = 2, 20Hz < f < 20kHz, RL = 8 Power Supply Rejection Ratio2 f = 217Hz, RL = 8, RFeed = 22K, Vripple = 200mV rms Phase Margin at Unity Gain RL = 8, CL = 500pF Gain Margin RL = 8, CL = 500pF Gain Bandwidth Product RL = 8 Min. Typ. 5.5 10 5 500 0.1 75 70 20 2 Max. 8 1000 20 Unit mA nA mV mW % dB Degrees dB MHz 1) Standby mode is actived when Vstdby is tied to Vcc 2) Dynamic measurements - 20*log(rms(Vout)/rms(Vripple)). Vripple is an added sinus signal to Vcc @ f = 217Hz 3. All electrical values are made by correlation between 2.6V and 5V measurements 4/30 Electrical Characteristics Table 5: VCC = 2.6V, GND = 0V, Tamb = 25C (unless otherwise specified) Symbol ICC ISTANDBY Voo Po THD + N PSRR M GM GBP Parameter Supply Current No input signal, no load Standby Current 1 No input signal, Vstdby = Vcc, RL = 8 Output Offset Voltage No input signal, RL = 8 Output Power THD = 1% Max, f = 1kHz, RL = 8 Total Harmonic Distortion + Noise Po = 200mW rms, Gv = 2, 20Hz < f < 20kHz, RL = 8 Power Supply Rejection Ratio2 f = 217Hz, RL = 8, RFeed = 22K, Vripple = 200mV rms Phase Margin at Unity Gain RL = 8, CL = 500pF Gain Margin RL = 8, CL = 500pF Gain Bandwidth Product RL = 8 Min. Typ. 5.5 10 5 300 0.1 75 70 20 2 Max. 8 1000 20 TS4972 Unit mA nA mV mW % dB Degrees dB MHz 1) Standby mode is actived when Vstdby is tied to Vcc 2) Dynamic measurements - 20*log(rms(Vout)/rms(Vripple)). Vripple is an added sinus signal to Vcc @ f = 217Hz Table 6: Components description Components Rin Cin Rfeed Cs Cb Cfeed Rstb Gv Functional Description Inverting input resistor which sets the closed loop gain in conjunction with Rfeed. This resistor also forms a high pass filter with Cin (fc = 1 / (2 x Pi x Rin x Cin)) Input coupling capacitor which blocks the DC voltage at the amplifier input terminal Feed back resistor which sets the closed loop gain in conjunction with Rin Supply Bypass capacitor which provides power supply filtering Bypass pin capacitor which provides half supply filtering Low pass filter capacitor allowing to cut the high frequency (low pass filter cut-off frequency 1 / (2 x Pi x Rfeed x Cfeed)) Pull-up resistor which fixes the right supply level on the standby pin Closed loop gain in BTL configuration = 2 x (Rfeed / Rin) Remarks: 1. All measurements, except PSRR measurements, are made with a supply bypass capacitor Cs = 100F. 2. External resistors are not needed for having better stability when supply @ Vcc down to 3V. By the way, the quiescent current remains the same. 3. The standby response time is about 1s. 5/30 TS4972 Figure 1: Open Loop Frequency Response 0 60 Gain Vcc = 5V RL = 8 Tamb = 25C -20 -40 -60 Phase (Deg) 40 Phase Gain (dB) Electrical Characteristics Figure 4: Open Loop Frequency Response 0 60 Gain Vcc = 5V ZL = 8 + 560pF Tamb = 25C -20 -40 -60 Phase (Deg) Phase (Deg) 40 Gain (dB) Phase 20 -80 -100 -120 -80 -100 -120 20 0 -140 -160 0 -140 -160 -20 -180 -200 -20 -180 -200 -40 0.3 1 10 100 Frequency (kHz) 1000 10000 -220 -40 0.3 1 10 100 1000 Frequency (kHz) 10000 -220 Figure 2: Open Loop Frequency Response 80 60 40 Gain (dB) Figure 5: Open Loop Frequency Response 80 60 40 Phase 20 0 -20 -40 0.3 Gain Vcc = 3.3V ZL = 8 + 560pF Tamb = 25C 0 -20 -40 -60 -80 -100 -120 -140 -160 -180 -200 -220 1 10 100 1000 Frequency (kHz) 10000 -240 Phase (Deg) 0 Gain Vcc = 33V RL = 8 Tamb = 25C -20 -40 -60 -100 -120 -140 -160 -180 -200 -220 -240 Phase (Deg) Gain (dB) -80 Phase 20 0 -20 -40 0.3 1 10 100 1000 Frequency (kHz) 10000 Figure 3: Open Loop Frequency Response 80 60 40 Gain (dB) Figure 6: Open Loop Frequency Response 80 Gain 60 40 Phase (Deg) Gain (dB) 0 Gain Vcc = 2.6V RL = 8 Tamb = 25C -20 -40 -60 -80 Phase -100 -120 -140 -160 -180 -200 -220 -240 0 Vcc = 2.6V ZL = 8 + 560pF Tamb = 25C -20 -40 -60 -80 Phase -100 -120 -140 -160 -180 -200 -220 -240 20 0 -20 -40 0.3 20 0 -20 -40 0.3 1 10 100 1000 Frequency (kHz) 10000 1 10 100 1000 Frequency (kHz) 10000 6/30 Electrical Characteristics Figure 7: Open Loop Frequency Response TS4972 Figure 10: Power Supply Rejection Ratio (PSRR) vs Power supply -30 Vripple = 200mVrms Rfeed = 22 Input = floating RL = 8 Tamb = 25C 100 80 60 Gain Gain (dB) -80 Phase -100 -40 -120 -140 -160 -180 Phase (Deg) PSRR (dB) 40 20 0 -20 -40 0.3 -50 -60 Vcc = 5V, 3.3V & 2.6V Cb = 1F & 0.1F Vcc = 5V CL = 560pF Tamb = 25C 1 10 100 1000 Frequency (kHz) 10000 -200 -220 -70 -80 10 100 1000 10000 Frequency (Hz) 100000 Figure 8: Open Loop Frequency Response Figure 11: Power Supply Rejection Ratio (PSRR) vs Bypass Capacitor -10 Cb=1F -20 Cb=10F -30 Phase (Deg) PSRR (dB) 100 80 60 Gain Gain (dB) -80 Phase -100 -120 -140 -160 Vcc = 5, 3.3 & 2.6V Rfeed = 22k Rin = 22k, Cin = 1F Rg = 100, RL = 8 Tamb = 25C Cb=47F 40 20 -180 0 -20 -40 0.3 Vcc = 2.6V CL = 560pF Tamb = 25C 1 10 100 1000 Frequency (kHz) 10000 -200 -220 -240 -40 -50 -60 -70 -80 10 Cb=100F 100 1000 Frequency (Hz) 10000 100000 Figure 9: Open Loop Frequency Response Figure 12: Power Supply Rejection Ratio (PSRR) vs Feedback Resistor -10 -20 -30 Phase (Deg) 100 80 60 Gain Gain (dB) -80 Phase -100 -120 PSRR (dB) -140 -160 40 20 -180 0 -20 -40 0.3 Vcc = 3.3V CL = 560pF Tamb = 25C 1 10 100 1000 Frequency (kHz) 10000 -200 -220 -240 -40 -50 -60 Vcc = 5, 3.3 & 2.6V Cb = 1F & 0.1F Vripple = 200mVrms Input = floating RL = 8 Tamb = 25C Rfeed=110k Rfeed=47k Rfeed=22k -70 Rfeed=10k -80 10 100 1000 10000 Frequency (Hz) 100000 7/30 TS4972 Figure 13: Power Supply Rejection Ratio (PSRR) vs Feedback Capacitor -10 -20 -30 PSRR (dB) Electrical Characteristics Figure 16: Power Dissipation vs Pout 1.4 Vcc = 5, 3.3 & 2.6V Cb = 1F & 0.1F Rfeed = 22k Vripple = 200mVrms Input = floating RL = 8 Tamb = 25C Cfeed=0 Cfeed=150pF Cfeed=330pF Power Dissipation (W) Vcc=5V 1.2 F=1kHz THD+N<1% 1.0 0.8 0.6 0.4 0.2 RL=16 0.0 0.0 RL=4 -40 -50 -60 -70 -80 10 RL=8 Cfeed=680pF 100 1000 10000 Frequency (Hz) 100000 0.2 0.4 0.6 0.8 1.0 1.2 Output Power (W) 1.4 1.6 Figure 14: Power Supply Rejection Ratio (PSRR) vs Input Capacitor -10 Cin=1F Cin=330nF -20 Cin=220nF Vcc = 5, 3.3 & 2.6V Rfeed = 22k, Rin = 22k Cb = 1F Rg = 100, RL = 8 Tamb = 25C Figure 17: Power Dissipation vs Pout 0.40 0.35 Vcc=2.6V F=1kHz THD+N<1% RL=4 Power Dissipation (W) 0.30 0.25 0.20 0.15 RL=8 0.10 0.05 RL=16 0.1 0.2 Output Power (W) 0.3 PSRR (dB) -30 -40 Cin=100nF -50 Cin=22nF -60 10 100 1000 Frequency (Hz) 10000 100000 0.00 0.0 0.4 Figure 15: Pout @ THD + N = 1% vs Supply Voltage vs RL 1.6 Figure 18: Pout @ THD + N = 10% vs Supply Voltage vs RL 2.0 Output power @ 10% THD + N (W) Output power @ 1% THD + N (W) 1.4 1.2 1.0 0.8 0.6 0.4 0.2 Gv = 2 & 10 Cb = 1F F = 1kHz BW < 125kHz Tamb = 25C 8 6 4 1.8 1.6 1.4 1.2 1.0 0.8 0.6 0.4 0.2 Gv = 2 & 10 Cb = 1F F = 1kHz BW < 125kHz Tamb = 25C 8 4 6 16 16 32 3.0 3.5 4.0 Power Supply (V) 4.5 5.0 32 3.0 3.5 4.0 Power Supply (V) 4.5 5.0 0.0 2.5 0.0 2.5 8/30 Electrical Characteristics Figure 19: Power Dissipation vs Pout 0.6 Vcc=3.3V F=1kHz 0.5 THD+N<1% Power Dissipation (W) TS4972 Figure 22: THD + N vs Output Power 10 RL = 4, Vcc = 3.3V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20kHz 0.1 RL=8 RL=4 0.4 0.3 0.2 0.1 RL=16 0.0 0.0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 THD + N (%) 1 20Hz 0.01 1E-3 0.01 0.1 Output Power (W) 1kHz 1 Output Power (W) Figure 20: Power Derating Curves Flip-Chip Package Power Dissipation (W) Figure 23: THD + N vs Output Power 10 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0.0 No Heat sink THD + N (%) Heat sink surface = 125mm (See demoboard) 2 1 RL = 4, Vcc = 2.6V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20kHz 0.1 20Hz 0 25 50 75 100 125 150 1kHz 0.01 1E-3 Ambiant Temperature ( C) 0.01 0.1 Output Power (W) Figure 21: THD + N vs Output Power 10 RL = 4 Vcc = 5V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C Figure 24: THD + N vs Output Power 10 RL = 4, Vcc = 5V Gv = 10 Cb = Cin = 1F BW < 125kHz, Tamb = 25C 20kHz THD + N (%) 20kHz THD + N (%) 1 1 0.1 20Hz 0.01 1E-3 1kHz 0.1 20Hz 1kHz 0.01 0.1 Output Power (W) 1 0.01 1E-3 0.01 0.1 Output Power (W) 1 9/30 TS4972 Figure 25: THD + N vs Output Power 10 RL = 4, Vcc = 3.3V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C Electrical Characteristics Figure 28: THD + N vs Output Power 10 RL = 8, Vcc = 3.3V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C THD + N (%) 0.1 20Hz THD + N (%) 1 20kHz 1 0.1 20Hz 20kHz 1kHz 1kHz 0.01 1E-3 0.01 0.1 Output Power (W) 1 0.01 1E-3 0.01 0.1 Output Power (W) 1 Figure 26: THD + N vs Output Power 10 RL = 4, Vcc = 2.6V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C Figure 29: THD + N vs Output Power 10 RL = 8, Vcc = 2.6V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C THD + N (%) 1 20Hz THD + N (%) 1 0.1 20kHz 0.1 20Hz 20kHz 1kHz 0.01 1E-3 0.01 0.1 Output Power (W) 0.01 1E-3 1kHz 0.01 0.1 Output Power (W) Figure 27: THD + N vs Output Power 10 RL = 8 Vcc = 5V Gv = 2 Cb = Cin = 1F 1 BW < 125kHz Tamb = 25C 20kHz 0.1 Figure 30: THD + N vs Output Power 10 RL = 8 Vcc = 5V Gv = 10 Cb = Cin = 1F 1 BW < 125kHz Tamb = 25C THD + N (%) THD + N (%) 20kHz 0.1 20Hz 0.01 1E-3 0.01 0.1 Output Power (W) 1kHz 1 0.01 1E-3 20Hz 0.01 0.1 Output Power (W) 1kHz 1 10/30 Electrical Characteristics Figure 31: THD + N vs Output Power 10 RL = 8, Vcc = 3.3V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20Hz 0.1 20kHz 1kHz 0.01 1E-3 0.01 0.1 Output Power (W) 1 0.01 1E-3 TS4972 Figure 34: THD + N vs Output Power 10 RL = 8, Vcc = 3.3V Gv = 2 Cb = 0.1F, Cin = 1F BW < 125kHz Tamb = 25C THD + N (%) THD + N (%) 1 1 0.1 20Hz 20kHz 1kHz 0.01 0.1 Output Power (W) 1 Figure 32: THD + N vs Output Power 10 RL = 8, Vcc = 2.6V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20Hz Figure 35: THD + N vs Output Power 10 RL = 8, Vcc = 2.6V Gv = 2 Cb = 0.1F, Cin = 1F BW < 125kHz Tamb = 25C THD + N (%) 1 THD + N (%) 1 0.1 20kHz 1kHz 0.01 1E-3 0.01 0.1 Output Power (W) 0.1 20Hz 20kHz 1kHz 0.01 1E-3 0.01 0.1 Output Power (W) Figure 33: THD + N vs Output Power 10 RL = 8 Vcc = 5V Gv = 2 Cb = 0.1F, Cin = 1F BW < 125kHz Tamb = 25C Figure 36: THD + N vs Output Power 10 RL = 8, Vcc = 5V, Gv = 10 Cb = 0.1F, Cin = 1F BW < 125kHz, Tamb = 25C THD + N (%) THD + N (%) 1 1 20Hz 20Hz 0.1 0.1 20kHz 20kHz 1kHz 0.01 0.1 Output Power (W) 1 0.01 1E-3 0.01 0.1 Output Power (W) 1 1kHz 0.01 1E-3 11/30 TS4972 Figure 37: THD + N vs Output Power 10 RL = 8, Vcc = 3.3V, Gv = 10 Cb = 0.1F, Cin = 1F BW < 125kHz, Tamb = 25C THD + N (%) THD + N (%) Electrical Characteristics Figure 40: THD + N vs Output Power 10 RL = 16, Vcc = 3.3V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 20Hz 20kHz 0.1 1 0.1 20Hz 20kHz 1kHz 0.01 0.01 1E-3 0.01 0.1 Output Power (W) 1 1kHz 0.01 Output Power (W) 0.1 1E-3 Figure 38: THD + N vs Output Power 10 RL = 8, Vcc = 2.6V, Gv = 10 Cb = 0.1F, Cin = 1F BW < 125kHz, Tamb = 25C THD + N (%) Figure 41: THD + N vs Output Power 10 RL = 16 Vcc = 2.6V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20kHz 0.1 1kHz 20Hz THD + N (%) 1 1 0.1 20Hz 20kHz 0.01 0.01 1E-3 0.01 Output Power (W) 0.1 1E-3 1kHz 0.01 Output Power (W) 0.1 Figure 39: THD + N vs Output Power 10 RL = 16, Vcc = 5V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C Figure 42: THD + N vs Output Power 10 RL = 16, Vcc = 5V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C THD + N (%) THD + N (%) 1 1 20kHz 0.1 20Hz 0.1 20Hz 20kHz 0.01 1E-3 1kHz 0.01 0.1 Output Power (W) 1 1kHz 0.01 1E-3 0.01 0.1 Output Power (W) 1 12/30 Electrical Characteristics Figure 43: THD + N vs Output Power 10 RL = 16 Vcc = 3.3V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20Hz 0.1 20kHz 1kHz 0.01 1E-3 0.01 Output Power (W) 0.1 0.01 20 100 Pout = 280mW 1000 Frequency (Hz) 1 RL = 4, Vcc = 3.3V Gv = 2 Cb = 1F BW < 125kHz Tamb = 25C Pout = 560mW 0.1 TS4972 Figure 46: THD + N vs Frequency THD + N (%) THD + N (%) 1 10000 Figure 44: THD + N vs Output Power 10 RL = 16 Vcc = 2.6V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20Hz 0.1 20kHz 1kHz 0.01 1E-3 0.01 Output Power (W) 0.1 Figure 47: THD + N vs Frequency 1 THD + N (%) THD + N (%) 1 RL = 4, Vcc = 2.6V Gv = 2 Cb = 1F BW < 125kHz Tamb = 25C 0.1 Pout = 240 & 120mW 0.01 20 100 1000 Frequency (Hz) 10000 Figure 45: THD + N vs Frequency Figure 48: THD + N vs Frequency 1 THD + N (%) THD + N (%) RL = 4, Vcc = 5V Gv = 2 Cb = 1F BW < 125kHz Tamb = 25C 1 Pout = 1.3W Pout = 1.3W 0.1 Pout = 650mW 0.1 RL = 4, Vcc = 5V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C 0.01 20 100 1000 Frequency (Hz) Pout = 650mW 0.01 20 100 1000 Frequency (Hz) 10000 10000 13/30 TS4972 Figure 49: THD + N vs Frequency Electrical Characteristics Figure 52: THD + N vs Frequency 1 Pout = 560mW THD + N (%) 0.1 THD + N (%) RL = 4, Vcc = 3.3V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C 1 Cb = 0.1F RL = 8, Vcc = 5V Gv = 10 Pout = 920mW BW < 125kHz Tamb = 25C 0.1 Pout = 280mW Cb = 1F 0.01 20 100 1000 Frequency (Hz) 10000 0.01 20 100 1000 Frequency (Hz) 10000 Figure 50: THD + N vs Frequency Figure 53: THD + N vs Frequency 1 1 THD + N (%) THD + N (%) RL = 4, Vcc = 2.6V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C Cb = 0.1F RL = 8, Vcc = 3.3V Gv = 2 Pout = 420mW BW < 125kHz Tamb = 25C 0.1 0.1 Pout = 240 & 120mW Cb = 1F 0.01 20 100 1000 Frequency (Hz) 10000 0.01 20 100 1000 Frequency (Hz) 10000 Figure 51: THD + N vs Frequency 1 RL = 8 Vcc = 5V Gv = 2 Pout = 920mW BW < 125kHz Tamb = 25C Figure 54: THD + N vs Frequency 1 RL = 8 Vcc = 5V Gv = 2 Pout = 460mW BW < 125kHz Tamb = 25C Cb = 0.1F Cb = 0.1F THD + N (%) THD + N (%) 0.1 0.1 Cb = 1F 0.01 20 100 1000 Frequency (Hz) 10000 0.01 20 Cb = 1F 100 1000 Frequency (Hz) 10000 14/30 Electrical Characteristics Figure 55: THD + N vs Frequency Figure 58: THD + N vs Frequency 1 TS4972 1 Cb = 0.1F THD + N (%) THD + N (%) RL = 8, Vcc = 5V Gv = 10 Pout = 460mW BW < 125kHz Tamb = 25C Cb = 0.1F 0.1 RL = 8, Vcc = 2.6V Gv = 2 Pout = 220mW BW < 125kHz Tamb = 25C 0.1 Cb = 1F 0.01 20 Cb = 1F 100 1000 Frequency (Hz) 10000 0.01 20 100 1000 Frequency (Hz) 10000 Figure 56: THD + N vs Frequency 1 RL = 8, Vcc = 3.3V Gv = 2 Pout = 210mW BW < 125kHz Tamb = 25C Figure 59: THD + N vs Frequency 1 Cb = 0.1F Cb = 0.1F THD + N (%) 0.1 THD + N (%) RL = 8, Vcc = 2.6V Gv = 10 Pout = 220mW BW < 125kHz Tamb = 25C 0.1 Cb = 1F Cb = 1F 0.01 20 100 1000 Frequency (Hz) 10000 0.01 20 100 1000 Frequency (Hz) 10000 Figure 57: THD + N vs Frequency Figure 60: THD + N vs Frequency 1 Cb = 0.1F THD + N (%) THD + N (%) RL = 8, Vcc = 3.3V Gv = 10 Pout = 420mW BW < 125kHz Tamb = 25C 1 Cb = 0.1F RL = 8, Vcc = 3.3V Gv = 10 Pout = 210mW BW < 125kHz Tamb = 25C 0.1 0.1 Cb = 1F 0.01 20 0.01 20 Cb = 1F 100 1000 Frequency (Hz) 10000 100 1000 Frequency (Hz) 10000 15/30 TS4972 Figure 61: THD + N vs Frequency 1 RL = 8, Vcc = 2.6V Gv = 10 Pout = 110mW BW < 125kHz Tamb = 25C Electrical Characteristics Figure 64: THD + N vs Frequency 0.1 THD + N (%) 0.1 THD + N (%) Cb = 0.1F Pout = 140mW 0.01 Pout = 280mW Cb = 1F 0.01 20 100 1000 Frequency (Hz) 10000 1E-3 20 100 RL = 16, Vcc = 3.3V Gv = 2, Cb = 1F BW < 125kHz Tamb = 25C 1000 Frequency (Hz) 10000 Figure 62: THD + N vs Frequency Figure 65: THD + N vs Frequency 0.1 1 Cb = 0.1F THD + N (%) THD + N (%) RL = 8, Vcc = 2.6V Gv = 10 Pout = 110mW BW < 125kHz Tamb = 25C Pout = 80mW 0.01 Pout = 160mW RL = 16, Vcc = 2.6V Gv = 2, Cb = 1F BW < 125kHz Tamb = 25C 0.1 Cb = 1F 0.01 20 100 1000 Frequency (Hz) 10000 1E-3 20 100 1000 Frequency (Hz) 10000 Figure 63: THD + N vs Frequency 0.1 Figure 66: THD + N vs Frequency Pout = 315mW THD + N (%) RL = 16, Vcc = 5V Gv = 10, Cb = 1F BW < 125kHz Tamb = 25C THD + N (%) 0.1 0.01 Pout = 315mW Pout = 630mW RL = 16, Vcc = 5V Gv = 2, Cb = 1F BW < 125kHz Tamb = 25C 1000 Frequency (Hz) 10000 0.01 20 Pout = 630mW 100 1000 Frequency (Hz) 10000 1E-3 20 100 16/30 Electrical Characteristics Figure 67: THD + N vs Frequency TS4972 Figure 70: Signal to Noise Ratio vs Power Supply with Weighted Filter Type A 110 1 RL = 16, Vcc = 3.3V Gv = 10, Cb = 1F BW < 125kHz Tamb = 25C 100 RL=16 RL=8 RL=4 THD + N (%) 0.1 Pout = 140mW Pout = 280mW SNR (dB) 90 80 Gv = 2 Cb = Cin = 1F THD+N < 0.4% Tamb = 25C 3.0 3.5 Vcc (V) 70 0.01 20 100 1000 Frequency (Hz) 10000 60 2.5 4.0 4.5 5.0 Figure 68: THD + N vs Frequency Figure 71: Frequency Response Gain vs Cin, & Cfeed 10 1 RL = 16, Vcc = 2.6V Gv = 10, Cb = 1F BW < 125kHz Tamb = 25C 5 Pout = 160mW Gain (dB) 0 -5 -10 -15 -20 Cfeed = 330pF Cfeed = 680pF Cin = 470nF Cin = 22nF Cin = 82nF Rin = Rfeed = 22k Tamb = 25C 10000 Cfeed = 2.2nF THD + N (%) 0.1 Pout = 80mW 0.01 20 100 1000 Frequency (Hz) 10000 -25 10 100 1000 Frequency (Hz) Figure 69: Signal to Noise Ratio vs Power Supply with Unweighted Filter (20Hz to 20kHz) 100 Figure 72: Signal to Noise Ratio vs Power Supply with Unweighted Filter (20Hz to 20kHz) 90 90 80 RL=16 SNR (dB) RL=8 RL=4 SNR (dB) 80 RL=8 70 RL=16 RL=4 70 Gv = 2 Cb = Cin = 1F THD+N < 0.4% Tamb = 25C 3.0 3.5 Vcc (V) 60 60 Gv = 10 Cb = Cin = 1F THD+N < 0.7% Tamb = 25C 3.0 3.5 Vcc (V) 50 2.5 4.0 4.5 5.0 50 2.5 4.0 4.5 5.0 17/30 TS4972 Figure 73: Signal to Noise Ratio vs Power Supply with Weighted Filter Type A 100 Electrical Characteristics Figure 76: Current Consumption vs Standby Voltage @ Vcc = 2.6V 6 5 Vcc = 2.6V Tamb = 25C 90 4 SNR (dB) RL=8 80 RL=16 RL=4 Icc (mA) 3 2 70 Gv = 10 Cb = Cin = 1F THD+N < 0.7% Tamb = 25C 3.0 3.5 Vcc (V) 1 0 0.0 60 2.5 4.0 4.5 5.0 0.5 1.0 1.5 Vstandby (V) 2.0 2.5 Figure 74: Current Consumption vs Power Supply Voltage 7 6 5 Icc (mA) Figure 77: Clipping Voltage vs Power Supply Voltage and Load Resistor 0.7 Vstandby = 0V Tamb = 25C Vout1 & Vout2 Clipping Voltage Low side (V) 0.6 0.5 0.4 Tamb = 25C RL = 4 4 3 2 1 0 RL = 8 0.3 0.2 0.1 RL = 16 0.0 2.5 0 1 2 Vcc (V) 3 4 5 3.0 3.5 4.0 4.5 5.0 Power supply Voltage (V) Figure 75: Current Consumption vs Standby Voltage @ Vcc = 5V 7 6 5 Icc (mA) Figure 78: Current Consumption vs Standby Voltage @ Vcc = 3.3V 6 Vcc = 5V Tamb = 25C 5 4 Icc (mA) Vcc = 3.3V Tamb = 25C 4 3 2 1 0 0.0 3 2 1 0 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 0.5 1.0 1.5 2.0 2.5 3.0 Vstandby (V) Vstandby (V) 18/30 Electrical Characteristics Figure 79: Clipping Voltage vs Power Supply Voltage and Load Resistor 0.6 TS4972 Vout1 & Vout2 Clipping Voltage High side (V) Tamb = 25C 0.5 0.4 RL = 4 RL = 8 0.3 0.2 0.1 RL = 16 0.0 2.5 3.0 3.5 4.0 4.5 5.0 Power supply Voltage (V) 19/30 TS4972 3 Application Information Application Information Figure 80: Demoboard Schematic S1 VCC VCC C1 Vcc S2 GND R2 GND R1 C2 VCC P1 Neg. Input 6 R3 C3 + C6 100 C7 100n U1 S6 R4 P2 Pos. Input C4 R5 C5 1 Vin- VC C Vout 1 8 OUT1 C9 + S3 GND S4 GND 7 Vin+ + 470 S5 Positive Input mode R6 S7 C10 Vout 2 4 + VCC 3 R7 100k S8 R8 1k Standby C11 + C12 + 1u G 2 ND C8 100n Bypass AV = -1 + OUT2 470 5 Standby Bias TS4972 Figure 81: Flip-Chip 300m Demoboard Components Side 20/30 Application Information Figure 82: Flip-Chip 300m Demoboard Top Solder Layer The output power is: Pout = (2 Vout RMS ) 2 (W) RL TS4972 For the same power supply voltage, the output power in BTL configuration is four times higher than the output power in single ended configuration. Gain In Typical Application Schematic (cf. page 1) In flat region (no effect of Cin), the output voltage of the first stage is: Rfeed Vout1 = Vin ------------------- (V) Rin For the second stage : Vout2 = -Vout1 (V) The differential output voltage is: The differential gain named gain (Gv) for more convenient usage is: Vout2 Vout1 Rfeed Gv = -------------------------------------- = 2 ------------------Rin Vin Remark : Vout2 is in phase with Vin and Vout1 is 180 phased with Vin. It means that the positive terminal of the loudspeaker should be connected to Vout2 and the negative to Vout1. Low and high frequency response In low frequency region, the effect of Cin starts. Cin with Rin forms a high pass filter with a -3dB cut off frequency. 1 FCL = ------------------------------- ( Hz ) 2 Rin Cin BTL Configuration Principle In high frequency region, you can limit the bandwidth by adding a capacitor (Cfeed) in parallel on Rfeed. Its form a low pass filter with a -3dB cut off frequency. 1 FCH = ---------------------------------------------- ( Hz ) 2 Rfeed Cfeed Power dissipation and efficiency * Voltage and current in the load are sinusoidal (Vout and Iout) * Supply voltage is a pure DC source (Vcc) Hypothesis : The TS4972 is a monolithic power amplifier with a BTL output type. BTL (Bridge Tied Load) means that each end of the load is connected to two single ended output amplifiers. Thus, we have : Single ended output 1 = Vout1 = Vout (V) Single ended output 2 = Vout2 = -Vout (V) And Vout1 - Vout2 = 2Vout (V) - - Figure 83: Flip-Chip 300m Demoboard Bottom Solder Layer Vout2 Rfeed Vout1 = 2Vin ------------------- (V) Rin - 21/30 TS4972 Regarding the load we have: VOUT = V PEAK sint (V) and VOUT IOUT = ---------------- (A) RL and VP EAK 2 POUT = ---------------------- (W) 2RL Then, the average current delivered by the supply voltage is: VPE AK ICC AVG = 2 ------------------- (A) RL The power delivered by the supply voltage is Psupply = Vcc IccAVG (W) Then, the power dissipated by the amplifier is Pdiss = Psupply - Pout (W) Application Information Cs has especially an influence on the THD+N in high frequency (above 7kHz) and indirectly on the power supply disturbances. With 100F, you can expect similar THD+N performances like shown in the datasheet. If Cs is lower than 100F, in high frequency increases, THD+N and disturbances on the power supply rail are less filtered. To the contrary, if Cs is higher than 100F, those disturbances on the power supply rail are more filtered. Cb has an influence on THD+N in lower frequency, but its function is critical on the final result of PSRR with input grounded in lower frequency. If Cb is lower than 1F, THD+N increase in lower frequency (see THD+N vs frequency curves) and the PSRR worsens up If Cb is higher than 1F, the benefit on THD+N in lower frequency is small but the benefit on PSRR is substantial (see PSRR vs. Cb curve : fig.12). Note that Cin has a non-negligible effect on PSRR in lower frequency. Lower is its value, higher is the PSRR (see fig. 13). Pop and Click performance Pop and Click performance is intimately linked with the size of the input capacitor Cin and the bias voltage bypass capacitor Cb. Size of Cin is due to the lower cut-off frequency and PSRR value requested. Size of Cb is due to THD+N and PSRR requested always in lower frequency. Moreover, Cb determines the speed that the amplifier turns ON. The slower the speed is, the softer the turn ON noise is. The charge time of Cb is directly proportional to the internal generator resistance 50k. Then, the charge time constant for Cb is b = 50kxCb (s) As Cb is directly connected to the non-inverting input (pin 2 & 3) and if we want to minimize, in amplitude and duration, the output spike on Vout1 (pin 5), Cin must be charged faster than Cb. The charge time constant of Cin is in = (Rin+Rfeed)xCin (s) and the maximum value is obtained when: Pdiss --------------------- = 0 POUT and its value is: Pdiss max = 2 Vcc 2 2RL Remark : This maximum value is only depending on power supply voltage and load values. The efficiency is the ratio between the output power and the power supply VPEAK POUT = ----------------------- = ---------------------Psupp ly 4VCC The maximum theoretical value is reached when Vpeak = Vcc, so ---- = 78.5% 4 Decoupling of the circuit Two capacitors are needed to bypass properly the TS4972, a power supply bypass capacitor Cs and a bias voltage bypass capacitor Cb. 22/30 - 2 2Vcc Pdiss = ---------------------- POUT RL POUT (W) (W) Application Information Thus we have the relation in << b (s) The respect of this relation permits to minimize the pop and click noise. Remark : Minimize Cin and Cb has a benefit on pop and click phenomena but also on cost and size of the application. Example : your target for the -3dB cut off frequency is 100 Hz. With Rin=Rfeed=22 k, Cin=72nF (in fact 82nF or 100nF). With Cb=1F, if you choose the one of the latest two values of Cin, the pop and click phenomena at power supply ON or standby function ON/OFF will be very small 50 kx1F >> 44kx100nF (50ms >> 4.4ms). Increasing Cin value increases the pop and click phenomena to an unpleasant sound at power supply ON and standby function ON/OFF. Why Cs is not important in pop and click consideration ? Hypothesis : * Cs = 100F * Supply voltage = 5V * Supply voltage internal resistor = 0.1 * Supply current of the amplifier Icc = 6mA At power ON of the supply, the supply capacitor is charged through the internal power supply resistor. So, to reach 5V you need about five to ten times the charging time constant of Cs (s = 0.1xCs (s)). Then, this time equal 50s to 100s << b in the majority of application. At power OFF of the supply, Cs is discharged by a constant current Icc. The discharge time from 5V to 0V of Cs is: 5Cs tDi schC s = ------------- = 83 ms Icc Now, we must consider the discharge time of Cb. At power OFF or standby ON, Cb is discharged by a 100k resistor. So the discharge time is about bDisch 3xCbx100k (s). In the majority of application, Cb=1F, then bDisch300ms >> tdischCs. Power amplifier design examples Given : TS4972 * Load impedance : 8 * Output power @ 1% THD+N : 0.5W * Input impedance : 10k min. * Input voltage peak to peak : 1Vpp * Bandwidth frequency : 20Hz to 20kHz (0, 3dB) * Ambient temperature max = 50C * SO8 package First of all, we must calculate the minimum power supply voltage to obtain 0.5W into 8. With curves in fig. 15, we can read 3.5V. Thus, the power supply voltage value min. will be 3.5V. Following equation the maximum power dissipation Pdiss max = 2 Vcc 2 2RL (W) with 3.5V we have Pdissmax=0.31W. Refer to power derating curves (fig. 20), with 0.31W the maximum ambient temperature will be 100C. This last value could be higher if you follow the example layout shown on the demoboard (better dissipation). The gain of the amplifier in flat region will be: VOUTPP 2 2RL POUT GV = -------------------- = ----------------------------------- = 5.65 VINPP VINPP We have Rin > 10k. Let's take Rin = 10k, then Rfeed = 28.25k. We could use for Rfeed = 30k in normalized value and the gain will be Gv = 6. In lower frequency we want 20 Hz (-3dB cut off frequency). Then: 1 CIN = ----------------------------- = 795nF 2 RinFCL So, we could use for Cin a 1F capacitor value which gives 16Hz. In Higher frequency we want 20kHz (-3dB cut off frequency). The Gain Bandwidth Product of the TS4972 is 2MHz typical and doesn't change when the amplifier delivers power into the load. The first amplifier has a gain of: Rfeed ----------------- = 3 Rin 23/30 TS4972 and the theoretical value of the -3dB cut-off higher frequency is 2MHz/3 = 660kHz. We can keep this value or limit the bandwidth by adding a capacitor Cfeed, in parallel on Rfeed. Then: 1 CFEED = -------------------------------------- = 265pF 2 RFEEDFCH So, we could use for Cfeed a 220pF capacitor value that gives 24kHz. Now, we can calculate the value of Cb with the formula b = 50kxCb >> in = (Rin+Rfeed)xCin which permits to reduce the pop and click effects. Then Cb >> 0.8F. We can choose for Cb a normalized value of 2.2F that gives good results in THD+N and PSRR. In the following tables, you could find three another examples with values required for the demoboard. Application n1 : 20Hz to 20kHz bandwidth and 6dB gain BTL power amplifier Components: Designator R1 R4 R6 R7 R8 C5 C6 C7 C9 C10 C12 S1, S2, S6, S7 S8 P1 Part Type 22k / 0.125W 22k / 0.125W Short Cicuit 100k / 0.125W Designator Short Circuit R1 470nF R2 100F R4 100nF R6 Short Circuit R7 Short Circuit R8 1F C2 2mm insulated Plug 10.16mm pitch 3 pts connector 2.54mm pitch SMB Plug C9 C5 C6 C7 P1 Application Information Application n2 : 20Hz to 20kHz bandwidth and 20dB gain BTL power amplifier Components: Designator R1 R4 R6 R7 R8 C5 C6 C7 C9 C10 C12 S1, S2, S6, S7 S8 Part Type 110k / 0.125W 22k / 0.125W Short Cicuit 100k / 0.125W Short Cicuit 470nF 100F 100nF Short Circuit Short Circuit 1F 2mm insulated Plug 10.16mm pitch 3 pts connector 2.54mm pitch SMB Plug Application n3 : 50Hz to 10kHz bandwidth and 10dB gain BTL power amplifier Components: Part Type 33k / 0.125W Short Circuit 22k / 0.125W Short Cicuit 100k / 0.125W Short Cicuit 470pF 150nF 100F 100nF Short Circuit 24/30 Application Information TS4972 For Vcc=5V, a 20Hz to 20kHz bandwidth and 20dB gain BTL power amplifier you could follow the bill of material below. Components: Designator R1 Part Type 110k / 0.125W 22k / 0.125W 22k / 0.125W 110k / 0.125W 100k / 0.125W Short circuit 470nF 470nF 100F 100nF Short Circuit Short Circuit 1F 2mm insulated Plug 10.16mm pitch 3 pts connector 2.54mm pitch SMB Plug Designator C10 C12 S1, S2, S6, S7 S8 P1 Part Type Short Circuit 1F 2mm insulated Plug 10.16mm pitch 3 pts connector 2.54mm pitch SMB Plug R4 R5 R6 R7 R8 C4 C5 C6 C7 C9 C10 C12 S1, S2, S6, S7 S8 P1, P2 Application n4 : Differential inputs BTL power amplifier In this configuration, we need to place these components : R1, R4, R5, R6, R7, C4, C5, C12. We have also : R4 = R5, R1 = R6, C4 = C5. The differential gain of the amplifier is: R1 GVDIFF = 2 ------R4 Note : Due to the VICM range (see Operating Condition), GVDIFF must have a minimum value shown in figure 84. Figure 84: Minimum Differential Gain vs Power Supply Voltage 40 35 Differential Gain min. (dB) 30 25 20 15 10 2.5 3.0 3.5 4.0 4.5 Power Supply Voltage (V) 5.0 5.5 25/30 TS4972 Note on how to use the PSRR curves (page 7) Application Information How we measure the PSRR ? Figure 86: PSRR measurement schematic We have finished a design and we have chosen the components values : * Rin=Rfeed=22k * Cin=100nF * Cb=1F Now, on fig. 13, we can see the PSRR (input grounded) vs frequency curves. At 217Hz we have a PSRR value of -36dB. In reality we want a value about -70dB. So, we need a gain of 34dB ! Now, on fig. 12 we can see the effect of Cb on the PSRR (input grounded) vs. frequency. With Cb=100F, we can reach the -70dB value. The process to obtain the final curve (Cb=100F, Cin=100nF, Rin=Rfeed=22k) is a simple transfer point by point on each frequency of the curve on fig. 13 to the curve on fig. 12. The measurement result is shown on the next figure. Figure 85: PSRR changes with Cb Rfeed Vripple 6 VCC 1 VinVout 1 Rin Cin 7 Vin+ + RL 8 Vs- Vcc AV = -1 3 Rg 100 Ohms Bypass + Vout 2 4 Vs+ 5 Standby Bias GND TS4972 Cb 2 Principle of operation * We fixed the DC voltage supply (Vcc) * We fixed the AC sinusoidal ripple voltage (Vripple) * No bypass capacitor Cs is used The PSRR value for each frequency is: -30 Cin=100nF Cb=1F Vcc = 5, 3.3 & 2.6V Rfeed = 22k, Rin = 22k Rg = 100, RL = 8 Tamb = 25C Rms ( Vri ppl e ) PSRR ( dB ) = 20 x Log 10 -------------------------------------------Rms ( Vs + - Vs - ) Remark : The measure of the Rms voltage is not a Rms selective measure but a full range (2 Hz to 125 kHz) Rms measure. It means that we measure the effective Rms signal + the noise. -40 PSRR (dB) -50 Cin=100nF Cb=100F -60 -70 10 100 1000 Frequency (Hz) 10000 100000 Note on PSRR measurement What is the PSRR? The PSRR is the Power Supply Rejection Ratio. It's a kind of SVR in a determined frequency range. The PSRR of a device, is the ratio between a power supply disturbance and the result on the output. We can say that the PSRR is the ability of a device to minimize the impact of power supply disturbances to the output. 26/30 Mechanical Data 4 Mechanical Data TS4972 Figure 87: TS4972 Footprint Recommendation (Non Solder Mask Defined) 500m =250m 500m 75m min. 100m max. Track Solder mask opening 500m 500m =400m 150m min. Pad in Cu 35m with Flash NiAu (6m, 0.15m) Figure 88: Top View Of The Daisy Chain Mechanical Data ( all drawings dimensions are in millimeters 7 Vin+ 6 Vcc 5 Stdby 8 Vout1 Vout2 4 1.6 mm Vin Gnd Bypass 1 2 2.26 mm 3 Remarks: Daisy chain sample is featuring pins connection two by two. The schematic above is illustrating the way connecting pins each other. This sample is used for testing continuity on board. PCB needs to be designed on the opposite way, where pin connections are not done on daisy chain samples. By that way, just connecting an Ohmeter between pin 8 and pin 1, the soldering process continuity can be tested. Order Codes Package Part Number TSDC03IJT Temperature Range J -40, +85C * DC3 Marking 27/30 TS4972 Figure 89: Tape & reel specification (top view) Mechanical Data 1 A A 1 All dimensions are in mm User direction of feed 28/30 5.1 5.1 D i e e s s i i z e e Y Y + + 7 0 0 m m 4 m07 + X ezis eiD m07 + X ezis eiD 4 8 Package Mechanical Data 5 Package Mechanical Data TS4972 5.1 Flip-Chip - 8 BUMPS 0.5 0.5 1.6 0.5 Die size : (2.26mm 10%) x (1.6mm 10%) Die height (including bumps) : 650m 50 Bumps diameter : 315m 15m Silicon thickness : 400m 25m Pitch: 500m 10m 0.5 2.26 400m 650m 250m Figure 90: Pin Out (top view) Figure 91: Marking (top view) E A72 YWW Balls are underneath 29/30 TS4972 Revision History Date January 2003 October 2004 Revision 1 2 First Release Package Mechanical Data Description of Changes Update Mechanical Data for Flip-Chip package Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications mentioned in this publication are subject to change without notice. This publication supersedes and replaces all information previously supplied. STMicroelectronics products are not authorized for use as critical components in life support devices or systems without express written approval of STMicroelectronics. The ST logo is a registered trademark of STMicroelectronics All other names are the property of their respective owners (c) 2004 STMicroelectronics - All rights reserved STMicroelectronics group of companies Australia - Belgium - Brazil - Canada - China - Czech Repubic - Finland - France - Germany - Hong Kong - India - Israel - Italy - Japan Malaysia - Malta - Morocco - Singapore - Spain - Sweden - Switzerland - United Kingdom - United States of America www.st.com 30/30 |
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