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U4090B
Monolithic Integrated Feature Phone Circuit
Description
The c-controlled telephone circuit U4090B is a linear integrated circuit for use in feature phones, answering machines and fax machines. It contains the speech circuit, tone ringer interface with DC/DC converter, sidetone equivalent and ear protection rectifiers. The circuit is line powered and contains all components necessary for amplification of signals and adaptation to the line. An integrated voice switch with loudspeaker amplifier allows loudhearing or hands-free operation. With an anti-feedback function, acoustical feedback during loudhearing can be reduced significantly. The generated supply voltage is suitable for a wide range of peripheral circuits.
Features
D DC characteristic adjustable D Transmit and receive gain adjustable D Symmetrical input of microphone amplifier D Anti-clipping in transmit direction D Automatic line-loss compensation D Symmetrical output of earpiece amplifier D Built-in ear protection D DTMF and MUTE input D Adjustable sidetone suppression independent of sending and receiving amplification D Speech circuit with two sidetone networks D Built-in line detection circuit D Integrated amplifier for loudhearing operation D Anti-clipping for loudspeaker amplifier D Improved acoustical feedback suppression D Power down D Voice switch D Tone ringer interface with dc/dc converter D Zero crossing detection D Common speaker for loudhearing and tone ringer D Supply voltages for all functional blocks of a subscriber set D Integrated transistor for short circuiting the line voltage D Answering machine interface D Operation possible from-10 mA line currents
Benefits
D Savings of one piezo-electric transducer D Complete system integration of analog signal processing on one chip D Very few external components
Applications
Feature phone, answering machine, fax machine, speaker phone
Block Diagram
Speech circuit Audio amplifier Loudhearing and Tone ringing
Voice switch
Tone ringer
MC with EEPROM/ DTMF
94 8741
Ordering Information
Extended Type Number U4090B-NFN U4090B-NFNG3 Rev. C2, 07-Mar-01 Package SSO44 SSO44 Remarks Taped and reeled 1 (31)
U4090B
Detailed Block Diagram
2 (31)
GT MICO TXIN IMPSEL 21 31 7 1 3 600 W 34 TXA 900 W Impedance control VL I L I Supply Line detect AGA control Q S Current supply Power supply V M 9 GND 6 PD 32 I REF 20 17 LIDET V RING 16 Receive attenuation RA2 -1 Mute receive control RA1 VMP + - + ST BAL - + - + 25 MUTX MUTR 35 36 40 41 39 38 37 STIL STIS 43 RECIN - 19 RFDO 18 THA 15 C OSC SW OUT 44 33 STO VL 8 AGA IND SENSE V B 11 10 V MP 14 V MPS 13 Transmit mute control RECO2 RECO1 GR RAC
94 8064
MIC1
5
MIC
MIC2
4
DTMF
DTMF
2
TTXA
42
TX ACL
INLDR 28
INLDT 27
TLDR
30
TLDT
29
26
Acoustical feedback suppression control
Figure 1. Detailed block diagram
ATAFS
12
SAO
SA
22
SACL
TSACL
24
SAI
SAI
23
Rev. C2, 07-Mar-01
GSA
U4090B
GT DTMF MICO MIC2 MIC1 PD IND VL GND SENSE VB SAO
Pin Description
1 2 3 4 5 6 7 8 9 10 11 44 43 42 41 40 39 38 37 36 35 34 TXIN RECIN TTXA GR RECO1 RAC STIL STIS RECO2 MUTR VM STO IREF AGA TLDR TLDT INLDR INLDT ATAFS MUTX SAI GSA 12 13 14 11 8 9 10 7 2 DTMF Pin 1 Symbol Function A resistor from this pin to GND sets the GT
amplification of microphone and DTMF signals,theinputamplifiercanbemuted by applying VMP to GT.
3 4 5 6
U4090B
12 33 32 31 30 29 28 27 26 25 24 23
94 7905 e
VMPS 13 VMP 14 SWOUT COSC VRING THA RFDO LIDET IMPSEL TSACL 15 16 17 18 19 20 21 22
15 16
Input for DTMF signals, also used for the answering machine and hands-free input MICO Output of microphone preamplifier MIC 2 Non-inverting input of microphone amplifier MIC 1 Inverting input of microphone amplifier PD Active high input for reducing the current consumption of the circuit, simultaneously VL is shorted by an internal switch IND The internal equivalent inductance of the circuit is proportional to the value of the capacitor at this pin, a resistor connected to ground may be used to reduce the dc line voltage VL Line voltage GND Reference point for dc- and ac-output signals SENSE A small resistor (fixed) connected from this pin to VL sets the slope of the dc characteristic and also effects the line-lengthequalization characteristics and the line current at which the loudspeaker amplifier is switched on VB Unregulated supply voltage for peripheral circuits (voice switch), limited to typically 7 V SAO Output of loudspeaker amplifier VMPS Unregulated supply voltage for C, limited to 6.3 V VMP Regulated supply voltage 3.3 V for peripheral circuits (especially microprocessors), minimum output current: 2 mA (ringing) 4 mA (speech mode) SWOUT Output for driving external switching transistor COSC 40-kHz oscillator for ringing power converter
Rev. C2, 07-Mar-01
3 (31)
U4090B
Pin 17 18 19 20 21 Symbol Function VRING Input for ringing signal protected by internal zener diode THA Threshold adjustment for ringing frequency detector RFDO Output of ringing frequency detector LIDET Line detect; output is low when the line current is more than 15 mA IMP- Control input for selection of line SEL impedance 1. 600 2. 900 3. Mute of second transmit stage (TXA); also used for indication of external supply (answering machine); last chosen impedance is stored TSACL Time constant of anti-clipping of speaker amplifier GSA Current input for setting the gain of the speaker amplifier, adjustment characteristic is logarithmical, or RGSA > 2 M, the speaker amplifier is switched off SA I Speaker amplifier input (for loudspeaker, tone ringer and hands-free use) MUTX Three-state input of transmit mute: 1) Speech condition; inputs MIC1 / MIC2 active 2) DTMF condition; input DTMF active a part of the input signal is passed to the receiving amplifier as a confidence signal during dialing 3) Input DTMF used for answering machine and hands-free use; receive branch not affected ATAFS Attenuation of acoustical feedback suppression, maximum attenuation of AFS circuit is set by a resistor at this pin, without the resistor, AFS is switched off INLDT Input of transmit level detector INLDR Input of receive level detector Pin 29 30 31 Symbol Function TLDT Time constant of transmit level detector TLDR Time constant of receive level detector AGA Automatic gain adjustment with line current a resistor connected from this pin to GND sets the starting point max. gain change: 6 dB. IREF Internal reference current generation; RREF = 62 k; IREF = 20 A STO Sidetone reduction output output resistance approx.: 300 , maximum load impedance: 10 k. VM Reference node for microphoneearphone and loudspeaker amplifier, supply for electret microphone (IM 700 mA) MUTR Three-state mute input 1. Normal operation 2. Mute of ear piece 3. Mute of RECIN signal Condition of earpiece mute is stored RECO 2 Inverting output of receiving amplifier STI S Input for sidetone network (short loop) or for answering machine STI L Input for sidetone network (long loop) RAC Input of receiving amplifier for ac coupling in feedback path RECO 1 Output of receiving amplifier GR A resistor connected from this pin to GNDsetsthereceivingamplification of the circuit; amplifier RA1 can be muted by applying VMP to GR TTXA Time constant of anti-clipping in transmit path RECIN Input of receiving path; input impedance is typically 80 kW TXIN Input of intermediate transmit stage, input resistance is typically 20 k
32 33
34
22 23
35
24
36 37 38 39 40 41
25
42 43 44
26
27 28
4 (31)
Rev. C2, 07-Mar-01
U4090B
DC Line Interface and Supply-Voltage Generation
The DC line interface consists of an electronic inductance and a dual-port output stage which charges the capacitors at VMPS and VB. The value of the equivalent inductance is given by: L = RSENSE CIND ((RDC R30) / (RDC + R30)) In order to improve the supply during worst-case operating conditions, two PNP current sources - IBOPT and IMPSOPT - hand an extra amount of current to the supply voltages when the NPNs in parallel are unable to conduct current. A flowchart for the control of the current sources (figure 3) shows how a priority for supply VMPS is achieved.
VL
10 W SENSE RSENSE CIND 10 m F IND RDC
+ - - + + -
IBOPT
< 5 mA
IMPSOPT
< 5 mA
6.3 V VMPS
=
3.3 V VMP 3.3 V/ 2 mA VB
470 m F
R30 30 kW
47 m F
=
94 8047
VOFFS
7.0 V
220 m F
Figure 2. DC line interface with electronic inductance and generation of a regulated and an unregulated supply
Y
VSENSE-VMPS>200 mV
VMPS < 6.3 V
N
N
Y VSENSE-VB>200 mV
N
IMPSOPT = 0 IBOPT = 0
Y N
VB < 6.3 V
Y Charge CMPS (IMPSOPT)
94 8058
Charge CB (IBOPT)
Reduce IBOPT (IMPSOPT = 0)
Figure 3. Supply capacitors CMPS and CB are charged with priority on CMPS
Rev. C2, 07-Mar-01
5 (31)
U4090B
VRING
RPC Voltage regulator
VB 7V VMP VMPS
VL
Power supply
Voltage regulator
6.3 V
QS PD ES IMPED
CONTR
IMPSEL
LIDET
LIDET
VLon
MIC, DTMF AGA, RA1, RA2 TX MUTE MUT REC, STBAL RECATT
RFDO
RFD
TXA TXACL
OFFSA COMP
SAI,SA SACL
AFS
94 8046
Figure 4. Supply of functional blocks is controlled by input voltages VL, VB, VRING and by logic inputs PD and IMPSEL
The U4090B contains two identical series regulators which provide a supply voltage VMP of 3.3 V suitable for a microprocessor. In speech mode, both regulators are active because VMPS and VB are charged simultaneously by the DC-line interface. Output current is 4 mA. The capacitor at VMPS is used to provide the microcomputer with sufficient power during long-line interruptions. Thus, long flash pulses can be bridged or a LCD display can be turned on for more than 2 seconds after going on hook. When the system is in ringing mode, VB is charged by the on-chip ringing power converter. In this mode only one regulator is used to supply VMP with max. 2 mA.
The special supply topology for the various functional blocks is illustrated in figure 4. There are four major supply states: 1. 2. 3. 4. Speech condition Power down (pulse dialing) Ringing External supply
Supply Structure of the Chip
As a major benefit the chip uses a very flexible system structure which allows simple realization of numerous applications such as: D Group listening phone D Hands-free phone D Ringing with the built in speaker amplifier D Answering machine with external supply
1. In speech condition the system is supplied by the line current. If the LIDET-block detects a line voltage above the fixed threshold (1.9 V), the internal signal VLON is activated, thus switching off RFD and RPC and switching on all other blocks of the chip. At line voltages below 1.9 V, the switches remain in their quiescent state as shown in the diagram. OFFSACOMP disables the group listening feature (SAI, SA, SACL, AFS) below line currents of approximately 10 mA. 2. When the chip is in power-down mode (PD = high), e.g., during pulse dialing, the internal switch QS shorts the line and all amplifiers are switched off. In this
6 (31)
Rev. C2, 07-Mar-01
U4090B
condition, LIDET, voltage regulators and IMPED CONTR are the only active blocks. 3. During ringing, the supply for the system is fed into VB via the ringing power converter (RPC). The only functional amplifiers are in the speaker amplifier section (SAI, SA, SACL). 4. In an answering machine, the chip is powered by an external supply via pin VB. This application allows the posibility to activate all amplifiers (except the transmit line interface TXA). Selecting IMPSEL = high impedance activates all switches at the ES line. circuit, which uses a modified voice switch topology. Figure 5 shows the basic system configuration. Two attenuators (TX ATT and RX ATT) reduce the critical loop gain by introducing an externally adjustable amount of loss either in the transmit or in the receive path. The sliding control in block ATT CONTR determines, whether the TX or the RX signal has to be attenuated. The overall loop gain remains constant under all operating conditions. Selection of the active channel is made by comparison of the logarithmically compressed TX- and RX- envelope curve. The system configuration for group listening, which is realized in the U4090B, is illustrated in figure 7. TXA and SAI represent the two attenuators, the logarithmic envelope detectors are shown in a simplified way (operational amplifiers with two diodes).
Acoustic Feedback Suppression
Acoustical feedback from the loudspeaker to the handset microphone may cause instability in the system. The U4090B offers a very efficient feedback suppression
TX Att Handset microphone Log Hybrid Att contr Line
Log
Loudspeaker
RX Att
94 8956
Figure 5. Basic voice switch system
Rev. C2, 07-Mar-01
7 (31)
U4090B
VL GT MICO TIN INLDT TLDT STO VL ZL
VBG
- +
TXA Zint
SAO
AFS control Max att. AGA
GSA SAI SAI TLDR - + VBG INLDR RECO1 GR STIS STO STN
94 8059
RECIN
Figure 6. Integration of acoustic feedback suppression circuit into the speech circuit environment
TLDT TXA SAI
TX
RLDT INLDT AGA AGA
RX
RLDR INLDR
IAGAFS IAT IATAFS IATGSA
94 8060
IGSA
TLDR RATAFS
ATAFS
GSA
Figure 7. Acoustic feedback suppression by alternative control of transmit- and speaker amplifier gain
8 (31)
Rev. C2, 07-Mar-01
U4090B
A detailed diagram of the AFS (acoustic feedback suppression) is given in figure 7. Receive and Transmit signals are first processed by logarithmic rectifiers in order to produce the envelopes of the speech at TLDT and RLDT. After amplification, a decision is made by the differential pair which direction should be transmitted. IL The attenuation of the controlled amplifiers TXA and SAI is determined by the emitter current IAT which is consists of three parts: IATAS IATGSA IAGAFS sets maximum attenuation decreases the attenuation when speaker amplifier gain is reduced decreases the attenuation according to the loop gain reduction caused by the AGA- function
94 8958
LIDET
PD
Figure 9. Line detection with two comparators for speech mode and pulse dialing
IAT = IATAFS - IATGSA - IAGAFS DG = IAT 0.67 dB/ mA Figure 8 illustrates the principle relationship between speaker amplifier gain (GSA) and attenuation of AFS (ATAFS). Both parameters can be adjusted independently, but the internal coupling between them has to be considered. Maximum usable value of GSA is 36 dB. The shape of the characteristic is moved in the x-direction by adjusting resistor RATAFS, thus changing ATAFSm. The actual value of attenuation (ATAFSa), however, can be determined by reading the value which belongs to the actual gain GSAa. If the speaker amplifier gain is reduced, the attenuation of AFS is automatically reduced by the same amount in order to achieve a constant loop gain. Zero attenuation is set for speaker gains GSA v GSA0 = 36 dB - ATAFSm.
Line Detection (LIDET)
The line current supervision is active under all operating conditions of the U4090B. In speech mode (PD = inactive), the line-current comparator uses the same thresholds as the comparator for switching off the entire speaker amplifier. The basic behavior is illustrated in figure 10. Actual values of ILON/ILOFF vary slightly with the adjustment of the DC characteristics and the selection of the internal line impedance. When Power Down is activated (during pulse dialing), the entire line current flows through the short-circuiting transistor QS (see figure 4). As long as IL is above typ. 1.6 mA, output LIDET is low. This comparator does not use hysteresis.
94 8957
94 8959
ATAFS (dB) ATAFS m ATAFS a RATAFS RATAFS not usable
LIDET
GSAo
GSA a
36 dB
GSA (dB)
ILOFF
ILON
IL
Figure 10. Line detection in speech mode with hysteresis Figure 8. Reducing speaker amplifier gain results in an equal reduction of AFS attenuation
Rev. C2, 07-Mar-01
9 (31)
U4090B
Ringing Power Converter (RPC)
The RPC transforms the input power at VRING (high voltage/ low current) into an equivalent output power at VB (low voltage/ high current) which is capable of driving the low-ohmic loudspeaker. Input impedance at VRING is fixed at 5 kW and the efficiency of the step-down converter is approx. 65%.
7 RDC= 6 VL ( V ) RDC=130kW 5 RDC=68kW
Ringing Frequency Detector (RFD)
The U4090B offers an output signal for the microcontroller, which is a digital representation of the double ringing frequency. It is generated by a current comparator with hysteresis. The input voltage VRING is transformed into a current via RTHA. The thresholds are 8 mA and 24 mA. RFDO and VRING are in phase. A second comparator with hysteresis is used to enable the output RFDO as long as the supply voltage for the microprocessor VMP is above 2.0 V.
4
3 10
94 9131
12
14
16
18
20
IL ( mA )
= ILON at line impedance = 600 W = ILOFF = ILON at line impedance = 900 W = ILOFF
Figure 11. Comparator thresholds depending on dc mask and line impedance
Absolute Maximum Ratings
Parameters Line current DC line voltage Maximum input current Junction temperature Ambient temperature Storage temperature Total power dissipation, Tamb = 60C Symbol IL VL IRING Tj Tamb Tstg Ptot Value 140 12 15 125 -25 to +75 -55 to +150 0.9 Unit mA V mA C C C W
Pin 17
Thermal Resistance
Junction ambient Parameters SSO44 Symbol RthJA Value 70 Unit K/W
10 (31)
Rev. C2, 07-Mar-01
U4090B
Electrical Characteristics
f = 1 kHz, 0 dBm = 775 mVrms, IM = 0.3 mA, IMP = 2 mA, RDC = 130 kW, Tamb = 25C, RGSA = 560 kW, Zear = 68 nF + 100 W, ZM = 68 nF, Pin 31 open, VIMPSEL = GND, VMUTX = GND, VMUTR = GND, unless otherwise specified. Parameters Test Conditions / Pin Symbol Min. DC characteristics DC voltage drop over circuit IL = 2 mA VL IL = 14 mA 4.6 IL = 60 mA IL = 100 mA 8.8 Transmission amplifier, IL = 14 mA, VMIC = 2 mV, RGT = 27 kW, unless Range of transmit gain GT 40 Transmitting amplification RGT = 12 kW 47 RGT = 27 kW GT 39.8 Frequency response IL w 14 mA, DGT f = 300 to 3400 Hz Gain change with current Pin 31 open DGT IL = 14 to 100 mA Gain deviation Tamb = -10 to +60C DGT CMRR of microphone CMRR 60 amplifier Input resistance of MIC RGT = 12 kW Ri amplifier RGT = 27 kW 45 Distortion at line IL > 14 mA dt VL = 700 mVrms IL > 19 mA, d < 5% VLmax 1.8 Maximum output voltage Vmic = 25 mV CTXA = 1 mF IMPSEL = open VMICOmax RGT = 12 kW Noise at line IL > 14 mA no psophometrically weighted GT = 48 dB Anti-clipping attack time CTXA = 1 mF release time each 3 dB overdrive Gain at low operating IL = 10 mA current IMP = 1 mA GT 40 RDC = 68 kW Vmic = 1 mV IM = 300 mA Distortion at low operating IL = 10 mA current IM = 300 mA dt IMP = 1 mA RDC = 68 kW Vmic = 10 mV Line loss compensation IL = 100 mA, DGTI -6.4 RAGA = 20 kW IL w 14 mA GTM 60 Mute suppression a) MIC muted (microphone Mutx = open preamplifier p p IMPSEL = open GTTX 60 b) TXA muted (second stage) Typ. 2.4 5.0 7.5 9.4 otherwise 45 48 Max. Unit Figure
5.4
V
20
10.0 specified 50 dB 49 dB 41.8 "0.5 dB "0.5 "0.5 dB dB dB kW 110 2 4.2 % dBm
21 21 21 21 21 21 21 21 21
80 50 75
3
-5.2
dBm
21 21
-80 0.5 9
-72
dBmp ms
21
42.5
dB
21
5
%
21
-5.8 80
-5.2
dB dB
21 21
dB
21
Rev. C2, 07-Mar-01
11 (31)
U4090B
Electrical Characteristics (continued)
Parameters Test Conditions / Pin Symbol Min. Typ. Max. Unit Receiving amplifier, IL = 14 mA, RGR = 62 k, unless otherwise specified, VGEN = 300 mV Adjustment range of IL w 14 mA, single GR -8 +2 dB receiving gain ended -2 +8 differential MUTR = GND Receiving amplification RGR = 62 kW GR - 1.75 -1 - 0.25 dB differential RGR = 22 kW 7.5 differential Amplification of DTMF sig- IL w 14 mA GRM 7 10 13 dB nal from DTMF IN to VMUTX = VMP RECO 1, 2 Frequency response IL > 14 mA, DGRF "0.5 dB f = 300 to 3400 Hz Gain change with current IL = 14 to 100 mA DGR "0.5 dB Gain deviation Tamb = -10 to +60C DGR "0.5 dB Ear-protection differential IL w 14 mA EP 2.2 Vrms VGEN = 11 Vrms MUTE suppression IL w 14 mA DGR 60 dB a) RECATT MUTR = open b) RA2 VMUTR = VMP c) DTMF operation VMUTX = VMP Output voltage d v 2% IL = 14 mA differential Zear = 68 nF + 100 W 0.775 Vrms Maximum output current Zear = 100 W 4 mA d v 2% (peak) Receiving noise Zear = 68 nF + 100 W ni -80 -77 dBmp psophometrically weighted IL w 14 mA Output resistance each output against Ro 10 W GND Line loss compensation RAGA = 20 kW, DGRI -7.0 -6.0 -5.0 dB IL = 100 mA Gain at low operating IL = 10 mA current IMP = 1 mA IM = 300 mA GR -2 -1 0 dB VGEN = 560 mV RDC = 68 kW AC impedance VIMPSEL = GND Zimp 570 600 640 W VIMPSEL = VMP Zimp 840 900 960 W Distortion at low operating IL = 10 mA current IMP = 1 mA dR 5 % VGEN = 560 mV RDC = 68 kW Figure 22
22
22
22 22 22 22 22
22 22 22 22 22
22
22
22
12 (31)
Rev. C2, 07-Mar-01
U4090B
Electrical Characteristics (continued)
Parameters Speaker amplifier Minimum line current for operation Input resistance Gain from SAI to SAO Test Conditions / Pin No ac signal Pin 24 VSAI = 3 mV, IL = 15 mA, RGSA = 560 kW RGSA = 20 kW Load resistance RL = 50 W, d < 5% VSAI = 20 mV IL = 15 mA IL = 20 mA IL > 15 mA Symbol ILmin 14 GSA dB 35.5 36.5 -3 37.5 23 Min. Typ. Max. 15 22 Unit mA kW Figure 23 23
Output power
23 PSA PSA nSA DGSA VSAO 3 7 20 200 "1 -60 mW mVpsoph 23
Output noise (Input SAI open) psophometrically weighted Gain deviation Mute suppression
Gain change with current DGSA "1 Resistor for turning off RGSA 0.8 1.3 2 speaker amplifier Gain change with frequency IL = 15 mA DGSA "0.5 f = 300 to 3400 Hz Attack time of anti-clipping 20 dB over drive tr 5 Release time of antitf 80 clipping DTMF amplifier Test conditions: IMP = 2 mA, IM = 0.3 mA, VMUTX = VMP Adjustment range of DTMF IL = 15 mA GD 40 50 gain Mute active DTMF amplification IL = 15 mA, GD 40.7 41.7 42.7 VDTMF = 8 mV Mute active: MUTX = VMP Gain deviaton IL = 15 mA GD "0.5 Tamb = -10 to +60 C Input resistance RGT = 27 kW, Ri 60 180 300 RGT = 15 kW 26 70 130 Distortion of DTMF signal IL w 15 mA dD 2 VL = 0 dBm Gain deviation with current IL = 15 to 100 mA DGD "0.5
IL = 15 mA Tamb = -10 to +60C IL = 15 mA, VL = 0 dBm, VSAI = 4 mV Pin 23 open IL = 15 to 100 mA IL = 15 to 100 mA
dB dBm
23 23
dB MW dB ms ms
23 23 23 23 23
dB dB
24 24
dB kW % dB
24 24 24 24
Rev. C2, 07-Mar-01
13 (31)
U4090B
Electrical Characteristics (continued)
Parameters Test Conditions / Pin Symbol AFS acoustic feedback suppression Adjustment range of IL w 15 mA attenuation Attenuation of transmit IL w 15 mA, DGT gain IINLDT = 0 mA RATAFS = 30 kW IINLDR = 10 mA Attenuation of speaker IL w 15 mA DGSA amplifier IINLDP = 0 m RATAFS = 30 kW IINLDR = 10 m AFS disable IL w 15 mA VATAFS Supply voltages, Vmic = 25 mV, Tamb = - 10 to + 60C VMP IL = 14 mA, VMP RDC = 68 kW IMP = 2 mA VMPS IL = 100 mA VMPS RDC = inf., IMP = 0 mA VM IL w 14 mA, VM IM = 700 mA RDC = 130 kW VB IB = + 20 mA, VB IL = 0 mA Ringing power converter, IMP = 1 mA, IM = 0 Maximum output power VRING = 20.6 V PSA Threshold of ring RFDO: low to high VRINGON frequency detector VHYST = VRINGON - RINGOFF VHYST Input impedance VRING = 30 V RRING Input impedance in speech f = 300 Hz to 3400 Hz RRINGSP mode IL > 15 mA,
VRING = 20V + 1.5Vrms
Min. 0
Typ.
Max. 50
Unit dB dB
Figure 23 23
45
50
dB
23
1.5 3.1 3.3 3.5
V V
23 20
6.7
V
20
1.3
3.3
V
20
7
7.6
V
20
20 17.5 11.0 5
mW V
25 25 25 25
4 150
6
kW kW
Logic level of frequency detector Ring detector enable Zener diode voltage
VRING = 0 V VB = 4 V VRING = 25 V VRING = 25 V, RFDO high IRING = 25 mA
VRFDO
0 VMP 2.0
V
25
VMPON
VRINGmax
1.8 30.8
2.2 33.3
V V
25 25
14 (31)
Rev. C2, 07-Mar-01
U4090B
Electrical Characteristics (continued)
Parameters MUTR Input MUTR input current Test Conditions / Pin VMUTR = GND IL > 14 mA VMUTR = VMP Mute low; IL > 14 mA Mute high; IL > 14 mA Symbol IMUTE Min. Typ. -20 +10 VMUTE VMUTE
VMP-0.3 V
Max. -30
Unit mA
Figure 26
MUTR input voltage
0.3
V V
26 26
PD Input PD input current
PD active, IL > 14 mA VPD = VMP Input voltage PD = active PD = inactive Voltage drop at VL IL = 14 mA, PD = active IL = 100 mA, PD = active Input characteristics of IMPSEL Input current IL w 14 mA VIMPSEL = VMP VIMPSEL = GND Input voltage Input high Input low MUTX input Input current Input voltage VMUTX = VMP VMUTX = GND Input high Input low Line detection Line current for LIDET active Line current for LIDET inactive Current threshold during power down PD = inactive PD = inactive VB = 5 V, PD = active
Ipd Vpd Vpd VL VL 2
9
uA V 0.3
26 26 26
1.5 1.9
V
IIMPSEL IIMPSEL VIMPSEL VIMPSEL IMUTX IMUTX VMUTX VMUTX ILON ILOFF ILONPD
18 -18
VMP-0.3 V
mA mA V 0.3 V mA mA V V mA mA 2.4 mA
26
26 26 26 26 26 20 20 20
20 -20
VMP-0.3 V
30 -30
0.3 12.6 11.0 0.8 1.6
Rev. C2, 07-Mar-01
15 (31)
U4090B
U4090B - Control
IMPSEL 0 Line-impedance = 600 W TXA = on ES = off Line-impedance = 600 W TXA = off ES = on Line-impedance = 900 W TXA = off ES = on Line-impedance = 900 W TXA = on ES = off MUTR RA2 = on RECATT = on STIS + STIL = on RA2 = on RECATT = off STIS = on, STIL = off RA2 = off RECATT = off STIS = on, STIL = off AGA off for STIS RA2 = off RECATT = on STIS + STIL = on
MODE Speech
MUTX 0 MIC 1/2 transmit enabled receive enable AFS = on AGA = on TXACL = on DTMF transmit enabled receive enable AFS = on AGA = on TXACL = on DTMF transmit enabled DTMF to receive enable AFS = off AGA = off TXACL = off
MODE Speech
0 to Z
Transmit-mute Z Transmit-mute
1 to Z
For answering machine
1
Speech 1
DTMF dialling
0
MODE Speech
Logic-level 0 = < (0.3 V) Z = > (1 V) < (VMP - 1 V) or (open input) 1 = > (VMP - 0.3 V)
0 to Z
For answering machine For answering machine
1 to Z
1
Speech + earpeace mute
RECATT = Receive attenuation STIS, STIL = Inputs of sidetone balancing amplifiers ES = External supply AFS = Acoustic feedback suppression control AGA = Automatic gain adjustment RA2 = Inverting receive amplifier TXACL = Transmit anti-clipping control
94 8856
Figure 12. Typical DC characteristic
16 (31)
Rev. C2, 07-Mar-01
U4090B
GT (dB)
RGT (kohm)
94 8860
Figure 13. Typical adjustment range of transmit gain
94 8859
Figure 14. Typical adjustment range of receive gain (differential output)
Rev. C2, 07-Mar-01
17 (31)
U4090B
948855
Figure 15. Typical AGA characteristic
94 8858
Figure 16. Typical load characteristic of VB for a maximum (RDC = infinity) DC-characteristic and 3-mW loudspeaker output
18 (31)
Rev. C2, 07-Mar-01
U4090B
94 8874
Figure 17. Typical load characteristic of VB for a medium DC-characteristic (RDC = 130 kW) and 3-mW loudspeaker output
94 8861
Figure 18. Typical load characteristic of VB for a minimum DC-characteristic (RDC = 68 kW) and 3-mW loudspeaker output
Rev. C2, 07-Mar-01
19 (31)
U4090B
Figure 19. Basic test circuit
1 10 W 600 W RDC S1 22 mF IL 220 m F 4.7 nF 47 m F 1000 m F
2
3
4
5
6
7
8
9
10
11
12
13
14 47 m F
15
16
17 68 nF
18
19 680 k W IMP
20
21 1 mF
22
RGT 10 m F 68 nF
1 kW
VM
50 W IDC
BC556 S2 open VRing 2.2 mH SD103A DC VMP
Rev. C2, 07-Mar-01
reference figure for not connected pins S1 = closed: speech mode S2 = closed: ringer mode
94 9132
20 (31)
VM 47 nF 36 kW VMP open 3 kW 3 kW VMP open RGR 10 m F IM ZEAR 10 m F 3.3 nF 28 30 29 10 m F 41 40 39 38 37 36 35 34 33 32 31 62 k W 2 MW 3.3 nF 27 26 25 24 23 100m F RGSA VM VM 47 nF 36 kW
Mico
VL
220 nF
150 nF
1m F
44
43
42
U4090B
1 68 nF 10m F 4.7 nF b IB RDC IL VL V DC VMP 10 W
2
3
4
5
6
7
8
9
10
11
12
13
14
15 IMP
16
17
18
19
20
21
22
RGT
220 m F 1000 m F 47 m F S1 open a VB
VLIDET
V
1m F
Figure 20. Test circuit for DC characteristics and line detection
VMIC
U4090B
Line detection: S1a VB (external supply): S1b open pins should be connected as shown in figure 25
94 9133
Rev. C2, 07-Mar-01
VM RGR RAGA IM 62 k W ZEAR 10m F 100m F 30 kW RGSA 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 24 23
Mico
VL
220 nF 150 nF 1 m F
44
43
42
41
U4090B
21 (31)
U4090B
1 68 nF S1 b S2 4.7 nF RDC IL Transmitting amplification GT = 20*log Vmic VCM 600 W V a 22 mF VL, dt, n o 25 k W a 10 mF 220 mF 10 W 1000 m F 47 m F I MP
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
21 1 mF V MP open
22
V RGTVMICO max
25 k W
VL Vmic
Figure 21. Test circuit for transmission amplifier
Line loss compensation: GTI = GT (at IL = 100 mA) -GT (at IL = 14 mA), S3 = closed D Gain change with current: GTI = GT (at IL = 100 mA) -GT (at IL = 14 mA) D Input resistance: Ri = 50 k VL (S2 = closed) -1 VL (S2 = open) VCM Common mode rejection ratio: CMRR = 20*log VL Mute suppression: GTM = 20*log VL (at MUTX = open) VL (at IMPSEL = low) GTTX = 20*log VL (at IMPSEL = open) open pins should be connected as shown in figure 25 + GT with S1b, S2 = closed,S3 = open VL (at MUTX = low)
AC
S1
b
1 mF
94 9135
22 (31)
open VM open V MP RGR RAGA IM S3 41 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 24 23 62 k W ZEAR 100 m F 10 mF V MP
Mico
VL
220 nF 150 nF
1 mF
44
43
42
U4090B
Rev. C2, 07-Mar-01
1 RGT
2
3
4
5 68 nF
6
7
8
9
10
11
12 1000 m F
13
14 47 m F
15 IMP
16
17
18
19
20
21
22
220 m F 10 m F 10 W
4.7 nF
1mF
VDTMF 220 nF S2 VM S1 b VGEN AC a 1 kW V
RDC 600 W
IL V VLR V MP open Line loss compensation: DGRI = GR (at IL = 100 mA) -GR (at IL = 14 mA), S3 = closed Receiving noise: S1a Receive amplification: GR = 20*log ( VZEAR/VLR) dB (S1 = b, S2 open) DTMF-control signal: GRM = 20*log (VZEAR/VDTMF) dB (S1 =a, S2 = closed) AC-impedance: (VLR/ (VGEN - VLR)) * ZL
22 m F
94 9134
Rev. C2, 07-Mar-01
Figure 22. Test circuit for receiving amplifier
open Mico VL VM 10 m F
220 nF 150 nF 1 mF
open VMP
VMP
RGR
VZEAR, dr
ZEAR
100m F
RAGA IM 62 k W S3 30 29 28 27 26 25 24 23
44
43
42
41
40
39
38
37
36
35
34
33
32
31
U4090B
U4090B
Mute suppression: a) RECATT: D GR = 20*log (VLR/VZEAR) dB +GR, MUTR = open b) RA2: D GR = 20*log (VLR/VZEAR) dB + GR, MUTR = VMP c) DTMF operation: D GR = 20*log VLR/VZEAR) dB + GR, MUTX = VMP open pins should be connected as shown in figure 25
23 (31)
U4090B
1 RGT
2
3
4 68 nF S1
5
6
7 10 mF
8
9
10
11
12
13
14 47 m F
15 IMP
16
17
18
19 VLIDET
20
21
22
220 m F RDC 10 W 47 m F
1000m F
V
1mF
VMIC 4.7 nF 22 m F 600 W IL V 50 W VSAO, S4 = closed VZIN, S4 = open n SA
VL
V
Input impedance: (VZIN/(VSAO - VZIN)) * RIN Gain from SAI to SAO: 20*log (VSAO / VSAI) dB VSAO RSAO Attenuation of transmit gain: S1 = closed Open pins should be connected as shown in figure 25 Output power: PSA =
2
94 9137
24 (31)
30 kW VM Mico 10 mF ZEAR 62 kW 10 mF 10 mF off S4 44 43 42 41 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 24 23 IINLDR IINLDT 220 nF
VATAFS
V
VSAI
220 nF 150 nF
1m F
RGR
20 kW
RGSA
Figure 23. Test circuit for speaker amplifier
U4090B
Rev. C2, 07-Mar-01
1 220 mF 1000 mF 47 mF
2
3
4
5
6
7
8
9
10
11
12
13
14
15 IMP
16
17
18
19
20
21
22
68 nF 10 mF VDTMF IL RDC 4.7 nF V VL: S3 = closed VL 50kW: S3 = open dD 10 W
Figure 24. Test circuit for DTMF amplifier
RGT
1 mF
220 nF
1kW
V
VM
S3
50 k W
DTMF-amplifier: 20log (VL/VDTMF) dB W Input resistance: (VL50K / (VL - VL50k)) * 50k Open pins should be connected as shown in figure 25
VGEN3
U4090B
AC
94 9136
Rev. C2, 07-Mar-01
VM VMP 10 m F 100 mF ZEAR IM 62 k W open 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25 24 23
Mico
VL
220 nF 150 nF 1 m F
RGR
44
43
42
41
U4090B
25 (31)
U4090B
1 47 mF 10 W VSAO RDC 4.7 nF 50 W IMP ramp IL VMP 47mF 1000 mF
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18 680 kW
19 V 68 nF
20 VRFDO
21
22 1 mF
68 nF
10 mF
Figure 25. Test circuit for ringing power converter
S5 V BC556
VRING IRING VRING 1.5 V 20 V
S1
S2
S3 IRING ramp
S4
220 mF
2.2 mH
20.6 V SD103A DC DC DC
94 9138
26 (31)
VSAI 1.8 Vpp 1 kHz 100 nF RGSA 30 29 28 27 26 25 24 23 100 m F 40 39 38 37 36 35 34 33 32 31 62 k W
1) Max. output power: PSA =
Vsao2 (S4 closed) RSAO 2) Threshold of ringing frequency detector: detecting VRFDO, when driving VRING from 2 V to 22 V (VRINGON) and back again (VRINGOFF) (S2 = closed) VRING 3) Input impedance: RRING = (S3 = closed) IRING Vring 4) Input impedance in speech mode (IL > 15 mA): RRINGSP = (S1 = closed) Iring 5) Ring detector enable: detecting VRFDO, when driving VMP from 0.7 V to 3.3 V (VMPON) and back again (VMPOFF) (S5, S3 = closed)
Open pins should be connected as shown in figure 25
44
43
42
41
U4090B
Rev. C2, 07-Mar-01
1
2 RGT
3
4
5 68 nF Ipd
6
7
8 10m F
9
10
10 W
11
12
13
14
47m F
15 IMP
16
17
18
19
20
21
22
1 mF
220m F 1000 m F
IIMPSEL
Vpd
4.7 nF RDC
VMP
V IL
VL
VMP
94 9139
Rev. C2, 07-Mar-01
VMP VM 10m F RGR 44 43 42 41 40 39 ZEAR 38 37 IMUTR 36 35 34
100 m F
VMP
Figure 26. Test circuit for input characteristics of I/O-ports
RGSA IM 33 32 62 kW 31 30 29 28 27 26 IMUTX 25 24 23
U4090B
Open pins should be connected as shown in figure 25
open
U4090B
27 (31)
U4090B
28 (31)
hook switch V M R1 R28 Micro- phone DTMF Generator C22 RECO C20 R20 MICO C19 R19 C18 1 5 4 2 42 28 27 30 3 44 C1 to ST to m C 33 8 21 31 7 10 11 14 13 34 9 6 32 20 17 16 15 Q1 C9 R6 VM C8 C2 12 V R2 C3
R3
Tip C7
C4 R4
C5
C6
Ring
Figure 27. Application circuit for loudhearing
R27 C21
R5
U4090B
Loudspeaker
C17 29 R31 26 12 C16 22 24
L1 19 R7 18 23 25 35 36 40 R11 41 39 C13 R10 V M Earpeace R9 C12 V M R8 C11 ST STN 2 (Option) 38 37 43 C10
V M R17 R16 R15
C15 C14 R14
R13 R12
Rev. C2, 07-Mar-01
V L
Micro controller
VMP
94 8849
VM hook switch C2 R1 12 V to ST 1 3 33 8 34 VM 4 C21 42 28 C18 30 C17 29 R18 12 22 C15 24 C14 R15 R14 R13 R12 R11 23 25 35 36 40 41 39 C13 R10 STN 2 (Option) Earpiece VM C12 VM R9 R8 C11 BC177 ST 38 37 43 C10 VB VL LOGTX R21 VMP 18 C16 26 19 R7 27 20 17 R6 2 9 6 32 21 31 7 10 44 11 14 13 5 to m C C8
R4
Tip C7
Rev. C2, 07-Mar-01
C3
R2
R25 R3
DTMF Micro- phone
R24
C25
C1
C4 C6
C5
R26
C23
HF-Mic R23
C24
Ring
R22
R5
RECO
C27 R30
R29
LOGTX
U4090B
16 15 Q1 C9
C26
L1
Figure 28. Application for hands-free operation
Loud speaker
VM
R17
R16
U4090B
94 8850
Micro- controller
29 (31)
U4090B
Table 6. Typical values of external components (figures 27 and 28)
Name C1 C2 C3 C4 C5 C6 C7 C8 C9 C10 C11 C12 C13 C14 C15
Value 100 nF 4.7 nF 10 mF 220 mF 47 mF 470 mF 820 nF 100 mF 100 nF 150 nF 86 nF 33 nF 10 mF 100 nF 1 mF
Name C16 C17 C18 C19 C20 C21 C22 C23 C24 C25 C26 C27 L1 R1 R2
Value 47 mF 10 mF 10 mF 68 nF 68 nF 1 mF 100 nF 6.8 nF 10 nF 100 nF 470 nF 33 nF 2.2 mH 27 kW 20 kW R3 R4 R5 R6 R7 R8 R9
Name
Value >68 kW 10 kW 1.5 kW 62 kW 680 kW 22 kW 330 kW 3 kW 62 kW 30 kW 62 kW 120 kW 47 kW 1 kW 1.2 kW
Name R18 R19 R20 R21 R22 R23 R24 R25 R26 R27 R28 R29 R30 R31
Value 30 kW 6.8 kW 6.8 kW 15 kW 330 kW 220 kW 68 kW 2 kW 3.3 kW 18 kW 2 kW 1 kW 12 kW 56 kW
R10 R11 R12 R13 R14 R15 R16 R17
Package Information
Package SSO44
Dimensions in mm
18.05 17.80 9.15 8.65 7.50 7.30
2.35 0.3 0.8 16.8 44 23 0.25 0.10
0.25 10.50 10.20
technical drawings according to DIN specifications 13040
1
22
30 (31)
Rev. C2, 07-Mar-01
U4090B
Ozone Depleting Substances Policy Statement
It is the policy of Atmel Germany GmbH to 1. Meet all present and future national and international statutory requirements. 2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems with respect to their impact on the health and safety of our employees and the public, as well as their impact on the environment. It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as ozone depleting substances (ODSs). The Montreal Protocol (1987) and its London Amendments (1990) intend to severely restrict the use of ODSs and forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these substances. Atmel Germany GmbH has been able to use its policy of continuous improvements to eliminate the use of ODSs listed in the following documents. 1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively 2. Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental Protection Agency (EPA) in the USA 3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C (transitional substances) respectively. Atmel Germany GmbH can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain such substances.
We reserve the right to make changes to improve technical design and may do so without further notice. Parameters can vary in different applications. All operating parameters must be validated for each customer application by the customer. Should the buyer use Atmel Wireless & Microcontrollers products for any unintended or unauthorized application, the buyer shall indemnify Atmel Wireless & Microcontrollers against all claims, costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death associated with such unintended or unauthorized use. Data sheets can also be retrieved from the Internet: http://www.atmel-wm.com
Atmel Germany GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany Telephone: 49 (0)7131 67 2594, Fax number: 49 (0)7131 67 2423
Rev. C2, 07-Mar-01
31 (31)

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