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TS4890
RAIL TO RAIL OUTPUT 1W AUDIO POWER AMPLIFIER WITH STANDBY MODE
s OPERATING FROM VCC = 2.2V to 5.5V s 1W RAI L TO RAIL OUTPUT POWER @
Vcc=5V, THD=1%, f=1kHz, with 8 Load PIN CONNECTIONS (Top View)
s ULTRA LOW CONSUMPTION IN STANDBY
MODE (10nA)
TS4890IS, TS4890IST - MiniSO8
s 75dB PSRR @ 217Hz from 5 to 2.2V s POP & CLICK REDUCTION CIRCUITRY s ULTRA LOW DISTORTION (0.1%) s UNITY GAIN STABLE s AVAILABLE IN MiniSO8 & SO8
DESCRIPTION The TS4890 (MiniSO8 & SO8) is an Audio Power Amplifier capable of delivering 1W of continuous RMS. ouput power into 8 load @ 5V. This Audio Amplifier is exhibiting 0.1% distortion level (THD) from a 5V supply for a Pout = 250mW RMS. An external standby mode control reduces the supply current to less than 10nA. An internal thermal shutdown protection is also provided. The TS4890 have been designed for high quality audio applications such as mobile phones and to minimize the number of external components. The unity-gain stable amplifier can be configured by external gain setting resistors. APPLICATIONS
Standby Bypass VIN+ VIN-
1 2 3 4
8 7 6 5
VOUT2 GND VCC VOUT1
TS4890ID, TS4890IDT - SO8
Standby Bypass VIN+ VIN-
1 2 3 4
8 7 6 5
VOUT2 GND VCC VOUT1
Audio Input Cin
Rin
4 3
VinVin+
+
Vcc
s Mobile Phones (Cellular / Cordless) s Laptop / Notebook Computers s PDAs s Portable Audio Devices
ORDER CODE
Part Number TS4890IST TS4890IDT Temperature Range -40, +85C Package S * * D
TYPICAL APPLICATION SCHEMATIC
Cfeed Rfeed Vcc 6 Cs
Vout1 5
RL 8 Ohms Vcc 2 1 Bypass Standby Bias GND TS4890 Av=-1 + Vout2 8
Rstb Cb
7
S = MiniSO Package (MiniSO) - also available in Tape & Reel (ST) D = Small Outline Package (SO) - also available in Tape & Reel (DT)
November 2001
1/31
TS4890
ABSOLUTE MAXIMUM RATINGS
Symbol VCC Vi Toper Tstg Tj R thja Supply voltage Input Voltage
2) 1)
Parameter
Value 6 GND to VCC -40 to + 85 -65 to +150 150
Unit V V C C C C/W
Operating Free Air Temperature Range Storage Temperature Maximum Junction Temperature Thermal Resistance Junction to SO8 MiniSO8 Power Dissipation 4) Human Body Model Machine Model Latch-up Immunity Lead Temperature (soldering, 10sec) Ambient3)
175 215 See Power Derating Curves Fig. 24 2 200 Class A 260 W kV V C
Pd ESD ESD
1. 2. 3. 4.
All voltages values are measured with respect to the ground pin. The magnitude of input signal must never exceed VCC + 0.3V / GND - 0.3V Device is protected in case of over temperature by a thermal shutdown active @ 150C. Exceeding the power derating curves during a long period may involve abnormal working of the device.
OPERATING CONDITIONS
Symbol VCC VICM VSTB RL R thja Supply Voltage Common Mode Input Voltage Range Standby Voltage Input : Device ON Device OFF Load Resistor Thermal Resistance Junction to Ambient SO8 MiniSO8
1)
Parameter
Value 2.2 to 5.5 GND + 1V to VCC 1.5 VSTB V CC GND V STB 0.5 4 - 32 150 190
Unit V V V C/W
1. This thermal resistance can be reduced with a suitable PCB layout (see Power Derating Curves Fig. 24)
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TS4890
ELECTRICAL CHARACTERISTICS VCC = +5V, GND = 0V, Tamb = 25C (unless otherwise specified)
Symbol ICC ISTANDBY Voo Po THD + N PSRR M GM GBP Parameter Supply Current No input signal, no load Standby Current 1) No input signal, Vstdby = GND, RL = 8 Output Offset Voltage No input signal, RL = 8 Output Power THD = 1% Max, f = 1kHz, RL = 8 Total Harmonic Distortion + Noise Po = 250mW rms, Gv = 2, 20Hz < f < 20kHz, RL = 8 Power Supply Rejection Ratio2) f = 217Hz, RL = 8, RFeed = 22K, Vripple = 200mV rms Phase Margin at Unity Gain RL = 8, CL = 500pF Gain Margin RL = 8, CL = 500pF Gain Bandwidth Product RL = 8 Min. Typ. 6 10 5 1 0.15 77 70 20 2 Max. 8 1000 20 Unit mA nA mV W % dB Degrees dB MHz
1. Standby mode is actived when Vstdby is tied to GND 2. Dynamic measurements - 20*log(rms(Vout)/rms(Vripple)). Vripple is the surimposed sinus signal to Vcc @ f = 217Hz
VCC = +3.3V, GND = 0V, Tamb = 25C (unless otherwise specified)
Symbol ICC ISTANDBY Voo Po THD + N PSRR M GM GBP Parameter Supply Current No input signal, no load Standby Current 1) No input signal, Vstdby = GND, RL = 8 Output Offset Voltage No input signal, RL = 8 Output Power THD = 1% Max, f = 1kHz, RL = 8 Total Harmonic Distortion + Noise Po = 250mW rms, Gv = 2, 20Hz < f < 20kHz, RL = 8 Power Supply Rejection Ratio2) f = 217Hz, RL = 8, RFeed = 22K, Vripple = 200mV rms Phase Margin at Unity Gain RL = 8, CL = 500pF Gain Margin RL = 8, CL = 500pF Gain Bandwidth Product RL = 8 Min. Typ. 5.5 10 5 450 0.15 77 70 20 2 Max. 8 1000 20 Unit mA nA mV mW % dB Degrees dB MHz
1. Standby mode is actived when Vstdby is tied to GND 2. Dynamic measurements - 20*log(rms(Vout)/rms(Vripple)). Vripple is the surimposed sinus signal to Vcc @ f = 217Hz
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TS4890
VCC = 2.6V, GND = 0V, Tamb = 25C (unless otherwise specified)
Symbol ICC ISTANDBY Voo Po THD + N PSRR M GM GBP Parameter Supply Current No input signal, no load Standby Current 1) No input signal, Vstdby = GND, RL = 8 Output Offset Voltage No input signal, RL = 8 Output Power THD = 1% Max, f = 1kHz, RL = 8 Total Harmonic Distortion + Noise Po = 200mW rms, Gv = 2, 20Hz < f < 20kHz, RL = 8 Power Supply Rejection Ratio2) f = 217Hz, RL = 8, RFeed = 22K, Vripple = 200mV rms Phase Margin at Unity Gain RL = 8, CL = 500pF Gain Margin RL = 8, CL = 500pF Gain Bandwidth Product RL = 8 Min. Typ. 5 10 5 260 0.15 77 70 20 2 Max. 8 1000 20 Unit mA nA mV mW % dB Degrees dB MHz
1. Standby mode is actived when Vstdby is tied to GND 2. Dynamic measurements - 20*log(rms(Vout)/rms(Vripple)). Vripple is the surimposed sinus signal to Vcc @ f = 217Hz
VCC = 2.2V, GND = 0V, Tamb = 25C (unless otherwise specified)
Symbol ICC ISTANDBY Voo Po THD + N PSRR M GM GBP Parameter Supply Current No input signal, no load Standby Current 1) No input signal, Vstdby = GND, RL = 8 Output Offset Voltage No input signal, RL = 8 Output Power THD = 1% Max, f = 1kHz, RL = 8 Total Harmonic Distortion + Noise Po = 200mW rms, Gv = 2, 20Hz < f < 20kHz, RL = 8 Power Supply Rejection Ratio2) f = 217Hz, RL = 8, RFeed = 22K, Vripple = 100mV rms Phase Margin at Unity Gain RL = 8, CL = 500pF Gain Margin RL = 8, CL = 500pF Gain Bandwidth Product RL = 8 Min. Typ. 5 10 5 180 0.15 77 70 20 2 Max. 8 1000 20 Unit mA nA mV mW % dB Degrees dB MHz
1. Standby mode is actived when Vstdby is tied to GND 2. Dynamic measurements - 20*log(rms(Vout)/rms(Vripple)). Vripple is the surimposed sinus signal to Vcc @ f = 217Hz
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TS4890
Components Rin Cin Rfeed Cs Cb Cfeed Rstb Gv
Functiona l Description Inverting input resistor which sets the closed loop gain in conjunction with Rfeed. This resistor also forms a high pass filter with Cin (fc = 1 / (2 x Pi x Rin x Cin)) Input coupling capacitor which blocks the DC voltage at the amplifier input terminal Feed back resistor which sets the closed loop gain in conjunction with Rin Supply Bypass capacitor which provides power supply filtering Bypass pin capacitor which provides half supply filtering Low pass filter capacitor allowing to cut the high frequency (low pass filter cut-off frequency 1 / (2 x Pi x Rfeed x Cfeed)) Pull-down resistor which fixes the right supply level on the standby pin Closed loop gain in BTL configuration = 2 x (Rfeed / Rin)
REMARKS 1. All measurements, except PSRR measurements, are made with a supply bypass capacitor Cs = 100F. 1. External resistors are not needed for having better stability when supply @ Vcc down to 3V. The quiescent current still remains the same. 2. The standby response time is about 1s.
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TS4890
Fig. 1 : Open Loop Frequency Response Fig. 2 : Open Loop Frequency Response
0 60 40
Gain (dB)
0 60 40
Phase (Deg) Gain (dB)
Gain
Vcc = 5V RL = 8 Tamb = 25 C
-20 -40 -60 -80 -100 -120 -140 -160 -180 -200 -220
Gain
Vcc = 5V ZL = 8 + 560pF Tamb = 25 C
-20 -40 -60 -100 -120 -140 -160 -180 -200 -220
Phase (Deg) Phase (Deg) Phase (Deg)
Phase 20 0 -20 -40 0.3
Phase 20 0
-80
-20 -40 0.3
1
10
100
Frequency (kHz)
1000
10000
1
10
100
Frequency (kHz)
1000
10000
Fig. 3 : Open Loop Frequency Response
Fig. 4 : Open Loop Frequency Response
80 60 40
Gain (dB)
0 Gain Vcc = 3.3V RL = 8 Tamb = 25 C -20 -40 -60
Phase (Deg) Gain (dB)
80 60 40 Phase 20 0 -20 -40 0.3 Gain Vcc = 3.3V ZL = 8 + 560pF Tamb = 25 C
0 -20 -40 -60 -80 -100 -120 -140 -160 -180 -200 -220 1 10 100
Frequency (kHz)
-80 Phase -100 -120 -140 -160 -180 -200 -220 -240
20 0
-20 -40 0.3
1
10
100
Frequency (kHz)
1000
10000
1000
10000
-240
Fig. 5 : Open Loop Frequency Response
Fig. 6 : Open Loop Frequency Response
80 60 40
Gain (dB)
0 Gain Vcc = 2.6V RL = 8 Tamb = 25 C -20 -40 -60 -80 Phase
Phase (Deg) Gain (dB)
80 Gain 60 40 Phase 20 0 -20 -40 0.3 Vcc = 2.6V ZL = 8 + 560pF Tamb = 25 C
0 -20 -40 -60 -80 -100 -120 -140 -160 -180 -200 -220 1 10 100
Frequency (kHz)
-100 -120 -140 -160 -180 -200 -220 -240
20 0 -20 -40 0.3
1
10
100
Frequency (kHz)
1000
10000
1000
10000
-240
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TS4890
Fig. 7 : Open Loop Frequency Response Fig. 8 : Open Loop Frequency Response
80 60 40
Gain (dB)
0 Gain Vcc = 2.2V RL = 8 Tamb = 25 C -20 -40 -60 -80 Phase
Phase (Deg) Gain (dB)
80 Gain 60 40 Phase 20 0 -20 -40 0.3 Vcc = 2.2V ZL = 8 + 560pF Tamb = 25 C
0 -20 -40 -60 -80 -100 -120 -140 -160 -180 -200 -220 1 10 100 1000 Frequency (kHz) 10000 -240
Phase (Deg) Phase (Deg) Phase (Deg)
-100 -120 -140 -160 -180 -200 -220 -240
20 0 -20 -40 0.3
1
10
100 1000 Frequency (kHz)
10000
Fig. 9 : Open Loop Frequency Response
Fig. 10 : Open Loop Frequency Response
100 80 60 Gain
Gain (dB)
-80 Phase -100 -120
100 80 60
Phase (Deg)
-80 Phase -100 -120 Gain -140 -160
40 20 0 -20 -40 0.3 Vcc = 5V CL = 560pF Tamb = 25 C 1 10 100
Frequency (kHz)
Gain (dB)
-140 -160 -180 -200
40 20 -180 0 -20 Vcc = 3.3V CL = 560pF Tamb = 25 C 1 10 100 1000 10000
Frequency (kHz)
-200 -220 -240
-220 1000 10000 -40 0.3
Fig. 11 : Open Loop Frequency Response
Fig. 12 : Open Loop Frequency Response
100 80 60
Gain (dB)
-80 Phase -100 -120
Phase (Deg)
100 80 60
Gain (dB)
-80 Phase -100 -120 Gain -140 -160
Gain 40
-140 -160
40 20 -180 0 -20 Vcc = 2.2V CL = 560pF Tamb = 25 C 1 10 100
Frequency (kHz)
20 -180 0 -20 Vcc = 2.6V CL = 560pF Tamb = 25 C 1 10 100
Frequency (kHz)
-200 -220 1000 10000 -240
-200 -220 1000 10000 -240
-40 0.3
-40 0.3
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TS4890
Fig. 13 : Power Supply Rejection Ratio (PSRR) vs Power supply Fig. 14 : Power Supply Rejection Ratio (PSRR) vs Feedback Capacitor
-30 -40
PSRR (dB)
-10 Vripple = 200mVrms Rfeed = 22k Input = floating RL = 8 Tamb = 25C Vcc = 5V to 2.2V Cb = 1F & 0.1F -20 -30
PSRR (dB)
-50 -60 -70 -80 10
-40 -50 -60 -70 -80 10
Vcc = 5 to 2.2V Cb = 1F & 0.1F Rfeed = 22k Vripple = 200mVrms Input = floating RL = 8 Tamb = 25C
Cfeed=0 Cfeed=150pF Cfeed=330pF
Cfeed=680pF 100 1000 10000 Frequency (Hz) 100000
100
1000 10000 Frequency (Hz)
100000
Fig. 15 : Power Supply Rejection Ratio (PSRR) vs Bypass Capacitor
-10 -20 -30
PSRR (dB)
Fig. 16 : Power Supply Rejection Ratio (PSRR) vs Input Capacitor
-10
Cb=1F Cb=10F
Vcc = 5 to 2.2V Rfeed = 22k Rin = 22k, Cin = 1F Rg = 100, RL = 8 Tamb = 25C Cb=47F
PSRR (dB)
Cin=1F Cin=330nF Cin=220nF
-20 -30 -40
Vcc = 5 to 2.2V Rfeed = 22k, Rin = 22k Cb = 1F Rg = 100, RL = 8 Tamb = 25C
-40 -50 -60 -70 Cb=100F -80 10 100 1000
Frequency (Hz)
Cin=100nF -50 -60 10 Cin=22nF
10000
100000
100
1000
Frequency (Hz)
10000
100000
Fig. 17 : Power Supply Rejection Ratio (PSRR) vs Feedback Resistor
Fig. 18 : Pout @ THD + N = 1% vs Supply Voltage vs RL
-10 -20 -30
PSRR (dB) Output power @ 1% THD + N (W)
1.4 Vcc = 5 to 2.2V Cb = 1F & 0.1F Vripple = 200mVrms Input = floating RL = 8 Tamb = 25C Rfeed=110k 1.2 1.0 0.8 16 0.6 0.4 0.2 0.0 2.5 32 3.0 3.5
Vcc (V)
Rfeed=47k
Gv = 2 & 10 Cb = 1 F F = 1kHz BW < 125kHz Tamb = 25 C
8 6 4
-40 -50 -60 -70 -80 10
Rfeed=22k Rfeed=10k 100 1000
Frequency (Hz)
10000
100000
4.0
4.5
5.0
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TS4890
Fig. 19 : Pout @ THD + N = 10% vs Supply Voltage vs RL Fig. 20 : Power Dissipation vs Pout
Output power @ 10% THD + N (W)
4
6
Power Dissipation (W)
2.0 Gv = 2 & 10 1.8 Cb = 1 F F = 1kHz 1.6 BW < 125kHz 1.4 Tamb = 25 C 1.2 1.0 0.8 0.6 0.4 0.2 0.0 2.5 3.0
1.4 8 Vcc=5V 1.2 F=1kHz THD+N<1% 1.0 0.8 0.6 0.4 0.2 RL=16 5.0 0.0 0.0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 RL=8
RL=4
16
32 3.5
Vcc (V)
4.0
4.5
Output Power (W)
Fig. 21 : Power Dissipation vs Pout
Fig. 22 : Power Dissipation vs Pout
0.6 Vcc=3.3V F=1kHz 0.5 THD+N<1%
Power Dissipation (W)
0.40 RL=4 Vcc=2.6V 0.35 F=1kHz THD+N<1% 0.30 0.25 0.20 0.15 RL=8 0.10 0.05 0.4
Output Power (W)
Power Dissipation (W)
RL=4
0.4 0.3 0.2 RL=8 0.1 RL=16 0.0 0.0 0.2 0.6 0.8
RL=16 0.1 0.2
Output Power (W)
0.00 0.0
0.3
0.4
Fig. 23 : Power Dissipation vs Pout
Fig. 24 : Power Derating Curves
0.40 Vcc=2.6V 0.35 F=1kHz THD+N<1% 0.30 RL=4 0.25 0.20 0.15 RL=8 0.10 0.05 0.00 0.0 RL=16 0.0 0.1 0.2
Output Power (W)
1.2 1.0 0.8 0.6 0.4 MiniSO8 0.2 SO8
SO8 on demoboard MiniSO8 on demoboard
Power Dissipation (W)
Power Dissipation (W)
0.3
0
25
50
75
100
125
150
Ambiant Temperature (C)
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TS4890
Fig. 25 : THD + N vs Output Power Fig. 26 : THD + N vs Output Power
10 Rl = 4 Vcc = 5V Gv = 2 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 1 20kHz
10 RL = 4, Vcc = 5V Gv = 10 Cb = Cin = 1 F BW < 125kHz, Tamb = 25 C
THD + N (%)
THD + N (%)
20kHz 1 20Hz
20Hz, 1kHz 0.1 1E-3 0.01 0.1 Output Power (W) 1 0.1 1E-3 0.01 0.1 Output Power (W)
1kHz 1
Fig. 27 : THD + N vs Output Power
Fig. 28 : THD + N vs Output Power
10 RL = 4, Vcc = 3.3V Gv = 2 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 1 20kHz
10 RL = 4, Vcc = 3.3V Gv = 10 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 1 20kHz
THD + N (%)
THD + N (%)
0.1 20Hz, 1kHz 0.1 1E-3 0.01 0.1 Output Power (W) 1 1E-3
20Hz 1kHz 0.01 0.1 Output Power (W) 1
Fig. 29 : THD + N vs Output Power
Fig. 30 : THD + N vs Output Power
10 RL = 4, Vcc = 2.6V Gv = 2 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 1
10 RL = 4, Vcc = 2.6V Gv = 10 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 1 20kHz
THD + N (%)
20kHz 0.1 20Hz, 1kHz 0.1 1E-3 0.01 0.1 Output Power (W) 1E-3
THD + N (%)
20Hz 1kHz 0.01 0.1 Output Power (W)
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TS4890
Fig. 31 : THD + N vs Output Power Fig. 32 : THD + N vs Output Power
10 RL = 4, Vcc = 2.2V Gv = 2 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 1
10 RL = 4, Vcc = 2.2V Gv = 10 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 1 20kHz
THD + N (%)
20kHz 0.1 20Hz, 1kHz 0.1 1E-3 0.01 Output Power (W) 0.1 1E-3
THD + N (%)
20Hz 1kHz 0.01 Output Power (W) 0.1
Fig. 33 : THD + N vs Output Power
Fig. 34 : THD + N vs Output Power
10 RL = 8 Vcc = 5V Gv = 2 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C
10 RL = 8 Vcc = 5V Gv = 10 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 20Hz 20kHz
THD + N (%)
THD + N (%)
1
1
20Hz, 1kHz
20kHz
0.1 1E-3 0.01 0.1 Output Power (W) 1
0.1 1kHz 1E-3 0.01 0.1 Output Power (W) 1
Fig. 35 : THD + N vs Output Power
Fig. 36 : THD + N vs Output Power
10 RL = 8, Vcc = 3.3V Gv = 2 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 1
10 RL = 8, Vcc = 3.3V Gv = 10 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 1 20Hz 20kHz
THD + N (%)
20Hz, 1kHz 0.1 1E-3
20kHz 0.1 1kHz
THD + N (%)
0.01 0.1 Output Power (W)
1
1E-3
0.01 0.1 Output Power (W)
1
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TS4890
Fig. 37 : THD + N vs Output Power Fig. 38 : THD + N vs Output Power
10 RL = 8, Vcc = 2.6V Gv = 2 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 1
10 RL = 8, Vcc = 2.6V Gv = 10 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 1 20Hz 20kHz
THD + N (%)
20Hz, 1kHz
20kHz 1kHz
0.1 1E-3 0.01 0.1 Output Power (W)
THD + N (%)
0.1 1E-3
0.01 0.1 Output Power (W)
Fig. 39 : THD + N vs Output Power
Fig. 40 : THD + N vs Output Power
10 RL = 8, Vcc = 2.2V Gv = 2 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 1
10 RL = 8, Vcc = 2.2V Gv = 10 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 1 20Hz 20kHz
THD + N (%)
1kHz 0.1 1E-3
20Hz
20kHz
THD + N (%)
0.1 0.01
Output Power (W)
1kHz 0.01
Output Power (W)
0.1
1E-3
0.1
Fig. 41 : THD + N vs Output Power
Fig. 42 : THD + N vs Output Power
10 RL = 8 Vcc = 5V Gv = 2 Cb = 0.1 F, Cin = 1 F BW < 125kHz Tamb = 25 C 20kHz 1kHz 20Hz
10 RL = 8, Vcc = 5V, Gv = 10 Cb = 0.1 F, Cin = 1 F BW < 125kHz, Tamb = 25 C 20Hz
THD + N (%)
THD + N (%)
1
1 20kHz
1kHz 0.1 1E-3 0.01 0.1 Output Power (W) 1 0.1 1E-3 0.01 0.1 Output Power (W) 1
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TS4890
Fig. 43 : THD + N vs Output Power Fig. 44 : THD + N vs Output Power
10 RL = 8, Vcc = 3.3V Gv = 2 Cb = 0.1 F, Cin = 1 F BW < 125kHz Tamb = 25 C 1 20Hz 20kHz 1kHz 0.1 1E-3 0.01 0.1 Output Power (W) 1
10 RL = 8, Vcc = 3.3V, Gv = 10 Cb = 0.1 F, Cin = 1 F BW < 125kHz, Tamb = 25 C
THD + N (%)
THD + N (%)
1 20kHz 20Hz
1kHz 0.1 1E-3 0.01 0.1 Output Power (W) 1
Fig. 45 : THD + N vs Output Power
Fig. 46 : THD + N vs Output Power
10 RL = 8, Vcc = 2.6V Gv = 2 Cb = 0.1 F, Cin = 1 F BW < 125kHz Tamb = 25 C 1 20Hz 20kHz 1kHz 0.1 1E-3 0.01 0.1 Output Power (W)
10 RL = 8, Vcc = 2.6V, Gv = 10 Cb = 0.1 F, Cin = 1 F BW < 125kHz, Tamb = 25 C
THD + N (%)
THD + N (%)
1 20kHz 20Hz
1kHz 0.1 1E-3 0.01 Output Power (W) 0.1
Fig. 47 : THD + N vs Output Power
Fig. 48 : THD + N vs Output Power
10 RL = 8, Vcc = 2.2V Gv = 2 Cb = 0.1 F, Cin = 1 F BW < 125kHz Tamb = 25 C 1 20Hz 20kHz 1kHz 0.1 1E-3 0.01
Output Power (W)
10 RL = 8, Vcc = 2.2V, Gv = 10 Cb = 0.1 F, Cin = 1 F BW < 125kHz, Tamb = 25 C
THD + N (%)
THD + N (%)
1 20kHz 20Hz
1kHz 0.1 0.1 1E-3 0.01
Output Power (W)
0.1
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TS4890
Fig. 49 : THD + N vs Output Power Fig. 50 : THD + N vs Output Power
10 RL = 16, Vcc = 5V Gv = 2 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C
10 RL = 16, Vcc = 5V Gv = 10 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 20kHz 0.1
THD + N (%)
20kHz 0.1
THD + N (%)
1
1
20Hz, 1kHz 0.01 1E-3 0.01 0.1 Output Power (W) 1 0.01 1E-3
1kHz
20Hz 1
0.01 0.1 Output Power (W)
Fig. 51 : THD + N vs Output Power
Fig. 52 : THD + N vs Output Power
10 RL = 16, Vcc = 3.3V Gv = 2 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C
10 RL = 16 Vcc = 3.3V Gv = 10 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 20kHz 0.1
THD + N (%)
20kHz 0.1
THD + N (%)
1
1
1kHz 20Hz, 1kHz 0.01 1E-3 0.01 Output Power (W) 0.1 0.01 1E-3
20Hz 0.01 Output Power (W) 0.1
Fig. 53 : THD + N vs Output Power
Fig. 54 : THD + N vs Output Power
10 RL = 16 Vcc = 2.6V Gv = 2 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 20kHz 0.1
10 RL = 16 Vcc = 2.6V Gv = 10 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 20Hz 0.1
THD + N (%)
THD + N (%)
1
1
20kHz
20Hz, 1kHz 0.01 1E-3 0.01 Output Power (W) 0.1 0.01 1E-3
1kHz 0.01 Output Power (W) 0.1
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TS4890
Fig. 55 : THD + N vs Output Power Fig. 56 : THD + N vs Output Power
10 RL = 16 Vcc = 2.2V Gv = 2 Cb = Cin = 1 F BW < 125kHz Tamb = 25 C 20Hz 0.1 20kHz
10 RL = 16 Vcc = 2.2V Gv = 10, Cb = Cin = 1 F BW < 125kHz, Tamb = 25 C
THD + N (%)
THD + N (%)
1
1 20kHz
0.1
1kHz 0.01 1E-3 0.01 Output Power (W) 0.1 0.01 1E-3
20Hz 1kHz 0.01 Output Power (W) 0.1
Fig. 57 : THD + N vs Frequency
Fig. 58 : THD + N vs Frequency
1
THD + N (%)
Pout = 1.2W
THD + N (%)
RL = 4, Vcc = 5V Gv = 2 Cb = 1F BW < 125kHz Tamb = 25C
Pout = 1.2W 1
0.1 RL = 4, Vcc = 5V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C 0.01 20 100 1000
Frequency (Hz)
Pout = 600mW
Pout = 600mW 0.1 20
100
1000
Frequency (Hz)
10000
10000
Fig. 59 : THD + N vs Frequency
Fig. 60 : THD + N vs Frequency
1
THD + N (%)
THD + N (%)
RL = 4, Vcc = 3.3V Gv = 2 Cb = 1F BW < 125kHz Tamb = 25C Pout = 540mW
1
RL = 4, Vcc = 3.3V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C Pout = 540mW
Pout = 270mW 0.1 20 100 1000
Frequency (Hz)
Pout = 270mW 10000 0.1 20 100 1000
Frequency (Hz)
10000
15/31
TS4890
Fig. 61 : THD + N vs Frequency Fig. 62 : THD + N vs Frequency
1
THD + N (%)
Pout = 240mW
THD + N (%)
RL = 4, Vcc = 2.6V Gv = 2 Cb = 1F BW < 125kHz Tamb = 25C
1
RL = 4, Vcc = 2.6V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C
Pout = 240 & 120mW
Pout = 120mW 0.1 20 100 1000
Frequency (Hz)
10000
0.1 20
100
1000
Frequency (Hz)
10000
Fig. 63 : THD + N vs Frequency
Fig. 64 : THD + N vs Frequency
1
THD + N (%)
THD + N (%)
RL = 4, Vcc = 2.2V Gv = 2 Cb = 1F BW < 125kHz Tamb = 25C Pout = 175mW
1
RL = 4, Vcc = 2.2V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C
Pout = 175mW
Pout = 88mW
Pout = 88mW 0.1 20 100 1000
Frequency (Hz)
10000
0.1 20
100
1000
Frequency (Hz)
10000
Fig. 65 : THD + N vs Frequency
Fig. 66 : THD + N vs Frequency
1 RL = 8 Vcc = 5V Gv = 2 Pout = 900mW BW < 125kHz Tamb = 25C
1 RL = 8 Vcc = 5V Gv = 2 Pout = 450mW BW < 125kHz Tamb = 25C Cb = 0.1F
THD + N (%)
Cb = 0.1F
Cb = 1F
THD + N (%)
Cb = 1F
0.1 20 100 1000
Frequency (Hz)
10000
0.1 20
100
1000
Frequency (Hz)
10000
16/31
TS4890
Fig. 67 : THD + N vs Frequency Fig. 68 : THD + N vs Frequency
1
THD + N (%)
THD + N (%)
RL = 8, Vcc = 5V Gv = 10 Pout = 900mW BW < 125kHz Tamb = 25C Cb = 0.1F
1
RL = 8, Vcc = 5V Gv = 10 Pout = 450mW BW < 125kHz Tamb = 25C Cb = 0.1F
Cb = 1F 0.1 20 100 1000 Frequency (Hz) 10000
Cb = 1F
0.1 20 100 1000
Frequency (Hz)
10000
Fig. 69 : THD + N vs Frequency
Fig. 70 : THD + N vs Frequency
1 RL = 8, Vcc = 3.3V Gv = 2 Pout = 400mW BW < 125kHz Tamb = 25C Cb = 0.1F
1 RL = 8, Vcc = 3.3V Gv = 2 Pout = 200mW BW < 125kHz Tamb = 25C Cb = 0.1F
THD + N (%)
Cb = 1F
THD + N (%)
Cb = 1F
0.1 20 100 1000
Frequency (Hz)
0.1 10000 20 100 1000
Frequency (Hz)
10000
Fig. 71 : THD + N vs Frequency
Fig. 72 : THD + N vs Frequency
1
THD + N (%)
Cb = 0.1F
THD + N (%)
RL = 8, Vcc = 3.3V Gv = 10 Pout = 400mW BW < 125kHz Tamb = 25C
1 Cb = 0.1F
RL = 8, Vcc = 3.3V Gv = 10 Pout = 200mW BW < 125kHz Tamb = 25C
Cb = 1F
Cb = 1F 0.1 0.1 20 100 1000 Frequency (Hz) 10000 20 100 1000
Frequency (Hz)
10000
17/31
TS4890
Fig. 73 : THD + N vs Frequency Fig. 74 : THD + N vs Frequency
1 RL = 8, Vcc = 2.6V Gv = 2 Pout = 220mW BW < 125kHz Tamb = 25C
1 RL = 8, Vcc = 2.6V Gv = 2 Pout = 110mW BW < 125kHz Tamb = 25C Cb = 0.1F
THD + N (%)
Cb = 0.1F
Cb = 1F
THD + N (%)
Cb = 1F
0.1 20 100 1000
Frequency (Hz)
0.1 10000 20 100 1000
Frequency (Hz)
10000
Fig. 75 : THD + N vs Frequency
Fig. 76 : THD + N vs Frequency
1
THD + N (%)
Cb = 0.1F
THD + N (%)
RL = 8, Vcc = 2.6V Gv = 10 Pout = 220mW BW < 125kHz Tamb = 25C
1 Cb = 0.1F
RL = 8, Vcc = 2.6V Gv = 10 Pout = 110mW BW < 125kHz Tamb = 25C
Cb = 1F
Cb = 1F 0.1 0.1 20 100 1000
Frequency (Hz)
10000
20
100
1000
Frequency (Hz)
10000
Fig. 77 : THD + N vs Frequency
Fig. 78 : THD + N vs Frequency
1 RL = 8, Vcc = 2.2V Gv = 2 Pout = 150mW BW < 125kHz Tamb = 25C
1 RL = 8, Vcc = 2.2V Gv = 2 Pout = 75mW BW < 125kHz Tamb = 25C Cb = 0.1F
THD + N (%)
Cb = 0.1F
Cb = 1F
THD + N (%)
Cb = 1F
0.1 20 100 1000
Frequency (Hz)
0.1 10000 20 100 1000
Frequency (Hz)
10000
18/31
TS4890
Fig. 79 : THD + N vs Frequency Fig. 80 : THD + N vs Frequency
1
THD + N (%)
Cb = 0.1F
THD + N (%)
RL = 8, Vcc = 2.2V Gv = 10 Pout = 150mW BW < 125kHz Tamb = 25C
1 Cb = 0.1F
RL = 8, Vcc = 2.2V Gv = 10 Pout = 75mW BW < 125kHz Tamb = 25C
Cb = 1F
Cb = 1F 0.1 0.1 20 100 1000
Frequency (Hz)
10000
20
100
1000
Frequency (Hz)
10000
Fig. 81 : THD + N vs Frequency
Fig. 82 : THD + N vs Frequency
1 RL = 16, Vcc = 5V Gv = 2, Cb = 1F BW < 125kHz Tamb = 25C
THD + N (%)
1 RL = 16, Vcc = 5V Gv = 10, Cb = 1F BW < 125kHz Tamb = 25C
THD + N (%)
Pout = 620mW
Pout = 310mW 0.1
0.1
Pout = 310mW Pout = 620mW
0.01 20
100
1000 Frequency (Hz)
10000
0.01 20
100
1000
Frequency (Hz)
10000
Fig. 83 : THD + N vs Frequency
Fig. 84 : THD + N vs Frequency
1 RL = 16, Vcc = 3.3V Gv = 2, Cb = 1F BW < 125kHz Tamb = 25C
THD + N (%)
1
Pout = 270mW 0.1
THD + N (%)
RL = 16, Vcc = 3.3V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C Pout = 270mW
0.1 Pout = 135mW Pout = 135mW 0.01 20 100 1000
Frequency (Hz)
10000
20
100
1000
Frequency (Hz)
10000
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TS4890
Fig. 85 : THD + N vs Frequency Fig. 86 : THD + N vs Frequency
1 RL = 16, Vcc = 2.6V Gv = 10, Cb = 1F BW < 125kHz Tamb = 25C
THD + N (%)
1 RL = 16, Vcc = 2.6V Gv = 2, Cb = 1F BW < 125kHz Tamb = 25C
THD + N (%)
Pout = 160mW Pout = 80mW 0.1
0.1
Pout = 80mW
Pout = 160mW
0.01 20
100
1000 Frequency (Hz)
10000
0.01 20
100
1000
Frequency (Hz)
10000
Fig. 87 : THD + N vs Frequency
Fig. 88 : THD + N vs Frequency
1 RL = 16, Vcc = 2.2V Gv = 2, Cb = 1F BW < 125kHz Tamb = 25C
THD + N (%) THD + N (%)
1 RL = 16, Vcc = 2.2V Gv = 10, Cb = 1F BW < 125kHz Tamb = 25C Pout = 50mW 0.1
Pout = 50 & 100mW 0.1
Pout = 100mW 0.01 20 100 1000
Frequency (Hz)
10000
0.01 20
100
1000
Frequency (Hz)
10000
Fig. 89 : Signal to Noise Ratio vs Power Supply with Unweighted Filter (20Hz to 20kHz)
Fig. 90 :Signal to Noise Ratio Vs Power Supply with Unweighted Filter (20Hz to 20kHz)
100
90
90 RL=16
SNR (dB)
80 RL=8 RL=4
SNR (dB)
80
RL=8 70 RL=16 Gv = 10 Cb = Cin = 1F THD+N < 0.7% Tamb = 25C 2.5 3.0 3.5 Vcc (V) 4.0 4.5 5.0 RL=4
70 Gv = 2 Cb = Cin = 1F THD+N < 0.4% Tamb = 25C 2.5 3.0 3.5
Vcc (V)
60
60
50 2.2
4.0
4.5
5.0
50 2.2
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TS4890
Fig. 91 : Signal to Noise Ratio vs Power Supply with Weighted Filter type A Fig. 92 : Signal to Noise Ratio vs Power Supply with Weighted Filter Type A
110
100
100 RL=8
SNR (dB)
90 RL=4
SNR (dB)
90
RL=16
RL=8 80 RL=16 RL=4
80 Gv = 2 Cb = Cin = 1F THD+N < 0.4% Tamb = 25C 2.5 3.0 3.5 Vcc (V) 4.0 4.5 5.0
70
70
Gv = 10 Cb = Cin = 1F THD+N < 0.7% Tamb = 25C 2.5 3.0 3.5 Vcc (V) 4.0 4.5 5.0
60 2.2
60 2.2
Fig. 93 : Frequency Response Gain vs Cin, & Cfeed
Fig. 94 : Current Consumption vs Power Supply Voltage (no load)
10 5 0
Gain (dB)
7 6 Cfeed = 330pF
Icc (mA)
Vstandby = Vcc Tamb = 25C
5 4 3 2
-5 -10 -15 -20 -25 10 Cin = 470nF Cin = 22nF Cin = 82nF
Cfeed = 680pF Cfeed = 2.2nF
Rin = Rfeed = 22k Tamb = 25 C 10000
1 0
100 1000 Frequency (Hz)
0
1
2
Vcc (V)
3
4
5
Fig. 95 : Current Consumption vs Standby Voltage @ Vcc = 5V
Fig. 96 : Current Consumption vs Standby Voltage @ Vcc = 3.3V
7 6 5
Icc (mA) Icc (mA)
6 5 4 3 2 1 0 0.0
4 3 2 1 0 0.0 Vcc = 5V Tamb = 25C 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
Vstandby (V)
Vcc = 3.3V Tamb = 25C 0.5 1.0 1.5 2.0 2.5 3.0
Vstandby (V)
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TS4890
Fig. 97 : Current Consumption vs Standby Voltage @ Vcc = 2.6V Fig. 98 : Current Consumption vs Standby Voltage @ Vcc = 2.2V
6 5 4
Icc (mA) Icc (mA)
5
4
3
3 2 1 0 0.0
2
1 Vcc = 2.6V Tamb = 25C 0.5 1.0 1.5 Vstandby (V) 2.0 2.5 0 0.0 0.5 1.0
Vstandby (V)
Vcc = 2.2V Tamb = 25 C 1.5 2.0
Fig. 99 : Clipping Voltage vs Power Supply Voltage and Load Resistor
Fig. 100 :Clipping Voltage vs Power Supply Voltage and Load Resistor
1.0 0.9
Vout1 & Vout2 Clipping Voltage High side (V)
1.0 Tamb = 25 C
Vout1 & Vout2 Clipping Voltage Low side (V)
0.9 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1
Tamb = 25 C
0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 0.0 2.2 2.5 3.0 3.5 4.0 RL = 16 4.5 5.0 RL = 4 RL = 8
RL = 4 RL = 8
RL = 16 2.5 3.0 3.5 4.0 4.5 5.0
0.0 2.2
Power supply Voltage (V)
Power supply Voltage (V)
22/31
TS4890
APPLICATION INFORMATION Fig. 101 : Demoboard Schematic
C1 R2 C2
R1 Vcc S1 Vcc Vcc S2 GND 6 C6 + 100 R3 Neg. input P1 R4 C4 Pos input P2 Vcc R7 1.5k S5 Positive Input mode R6 S8 Standby 2 1 Bypass Standby Bias Av=-1 + Vout2 8 C10 + 470 C5 R5 4 3 VinVin+ + C3 C7 100n
Vcc
S6 C9 + 470 OUT1 S3 GND S4 GND S7
Vout1 5
GND
TS4890
R8 10k
D1 PW ON + C11 + C12 1u C8
7
Fig. 102 : SO8 & MiniSO8 Demoboard Components Side
23/31
TS4890
Fig. 103 : SO8 & MiniSO8 Demoboard Top Solder Layer The output power is : Pout = (2 VoutRMS )2 (W) RL
For the same power supply voltage, the output power in BTL configuration is four times higher than the output power in single ended configuration.
s Gain In Typical Application Schematic
(cf. page 1) In flat region (no effect of Cin), the output voltage of the first stage is : Rfeed Vout1 = -Vin (V) Rin For the second stage : Vout2 = -Vout1 (V) Fig. 104 : SO8 & MiniSO8 Demoboard Bottom
Solder Layer
The differential output voltage is Rfeed Vout 2 - Vout1 = 2 Vin (V) Rin The differential gain named gain (Gv) for more convenient usage is : Gv = Vout 2 - Vout1 Rfeed =2 Vin Rin
Remark : Vout2 is in phase with Vin and Vout1 is 180 phased with Vin. It means that the positive terminal of the loudspeaker should be connected to Vout2 and the negative to Vout1.
s Low and high frequency response
In low frequency region, the effect of Cin starts. Cin with Rin forms a high pass filter with a -3dB cut off frequency . FCL = 1 2RinCin (Hz)
s BTL Configuration Principle
The TS4890 is a monolithic power amplifier with a BTL output type. BTL (Bridge Tied Load) means that each end of the load are connected to two single ended output amplifiers. Thus, we have : Single ended output 1 = Vout1 = Vout (V) Single ended output 2 = Vout2 = -Vout (V) And Vout1 - Vout2 = 2Vout (V)
24/31
In high frequency region, you can limit the bandwidth by adding a capacitor (Cfeed) in parallel on Rfeed. Its form a low pass filter with a -3dB cut off frequency . 1 FCH = (Hz) 2 Rfeed Cfeed
TS4890 s Power dissipation and efficiency
Hypothesis : * Voltage and current in the load are sinusoidal (Vout and Iout) * Supply voltage is a pure DC source (Vcc) Regarding the load we have : VOUT = VPEAK sin t (V) and IOUT = and POUT V = PEAK (W) 2 RL
2
The maximum theoretical value is reached when Vpeak = Vcc, so = 78.5% 4
s Decoupling of the circuit
Two capacitors are needed to bypass properly the TS4890. A power supply bypass capacitor Cs and a bias voltage bypass capacitor Cb. Cs has especially an influence on the THD+N in high frequency (above 7kHz) and indirectly on the power supply disturbances. With 100F, you can expect similar THD+N performances like shown in the datasheet. If Cs is lower than 100F, in high frequency increase THD+N and disturbances on the power supply rail are less filtered. To the contrary, if Cs is higher than 100F, those disturbances on the power supply rail are more filtered. Cb has an influence on THD+N in lower frequency, but its function is critical on the final result of PSRR with input grounded in lower frequency. If Cb is lower than 1F, THD+N increase in lower frequency (see THD+N vs frequency curves) and the PSRR worsens up If Cb is higher than 1F, the benefit on THD+N in lower frequency is small but the benefit on PSRR is substantial (see PSRR vs. Cb curves). Note that Cin has a non-negligible effect on PSRR in lower frequency. Lower is its value, higher is the PSRR (see fig. 13).
VOUT ( A) RL
Then, the average current delivered by the supply voltage is V Icc AVG = 2 PEAK (A) RL The power delivered by the supply voltage is Psupply = Vcc IccAVG (W) Then, the power dissipated by the amplifier is Pdiss = Psupply - Pout (W)
Pdiss = 2 2 Vcc RL POUT - POUT (W )
and the maximum value is obtained when Pdiss =0 POUT and its value is Pdiss max = 2 Vcc 2 2RL (W)
s Pop and Click performance
In order to have the best performances with the pop and click circuitry, the formula below must be follow : in b With in = (Rin + Rfeed ) x Cin (s) and b = 50k x Cb (s)
Remark : This maximum value is only depending on power supply voltage and load values. The efficiency is the ratio between the output power and the power supply POUT VPEAK = = P sup ply 4 Vcc
25/31
TS4890 s Power amplifier design examples
Given : * Load impedance : 8 * Output power @ 1% THD+N : 0.5W * Input impedance : 10k min. * Input voltage peak to peak : 1Vpp * Bandwidth frequency : 20Hz to 20kHz (0, -3dB) * THD+N in 20Hz to 20kHz < 0.5% @Pout=0.45W * Ambient temperature max = 50C * SO8 package First of all, we must calculate the minimum power supply voltage to obtain 0.5W into 8. See curves in fig. 15, we can read 3.5V. Thus, the power supply voltage value min. will be 3.5V. Following the equation : maximum power dissipation The first amplifier has a gain of Rfeed =3 Rin and the theoretical value of the -3dB cut of higher frequency is 2MHz/3 = 660kHz. We can keep this value or limiting the bandwidth by adding a capacitor Cfeed, in parallel on Rfeed. Then CFEED = 1 2 RFEED FCH = 265pF
So, we could use for Cfeed a 220pF capacitor value that gives 24kHz. Now, we can choose the value of Cb with the constraint THD+N in 20Hz to 20kHz < 0.5% @ Pout=0.45W. If you refer to the closest THD+N vs frequency measurement : fig. 71 (Vcc=3.3V, Gv=10), with Cb = 1F, the THD+N vs frequency is always below 0.4%. As the behaviour is the same with Vcc = 5V (fig. 67), Vcc = 2.6V (fig. 67). As the gain for these measurements is higher (worst case), we can consider with Cb = 1F, Vcc = 3.5V and Gv = 6, that the THD+N in 20Hz to 20kHz range with Pout = 0.45W will be lower than 0.4%. In the following tables, you could find three another examples with values required for the demoboard. Remark : components with (*) marking are optional. Application n1 : 20Hz to 20kHz bandwidth and 6dB gain BTL power amplifier. Components :
Designator R1 R4 R6 R7* R8 C5 C6 Part Type 22k / 0.125W 22k / 0.125W Short Cicuit (Vcc-Vf_led)/If_led 10k / 0.125W 470nF 100F
Pdiss max =
2 Vcc2 2RL
(W)
with 3.5V we have Pdissmax=0.31W. Refer to power derating curves (fig. 24), with 0.31W the maximum ambient temperature will be 100C. This last value could be higher if you follow the example layout shows on the demoboard (better dissipation). The gain of the amplifier in flat region will be : GV = VOUTPP 2 2RLPOUT = = 5.65 VINPP VINPP
We have Rin > 10k. Let's take Rin = 10k, then Rfeed = 28.25k. We could use for Rfeed = 30k in normalized value and the gain will be Gv = 6. In lower frequency we want 20 Hz (-3dB cut off frequency). Then CIN = 1 = 795nF 2 Rin FCL
So, we could use for Cin a 1F capacitor value that gives 16Hz. In Higher frequency we want 20kHz (-3dB cut off frequency). The Gain Bandwidth Product of the TS4890 is 2MHz typical and doesn't change when the amplifier delivers power into the load.
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TS4890
Application n3 : 50Hz to 10kHz bandwidth and 10dB gain BTL power amplifier. Components :
Designator C10 C12 S1, S2, S6, S7 S8 P1 D1* U1 Short Circuit 1F 2mm insulated Plug 10.16mm pitch 3 pts connector 2.54mm pitch PCB Phono Jack R8 Led 3mm C2 TS4890ID or TS4890IS C5 150nF 100F 100nF Short Circuit Short Circuit 1F 2mm insulated Plug 10.16mm pitch 3 pts connector 2.54mm pitch PCB Phono Jack Led 3mm TS4890ID or TS4890IS C6 C7 470pF 10k / 0.125W R1 R2 R4 R6 R7* 33k / 0.125W Short Circuit 22k / 0.125W Short Cicuit (Vcc-Vf_led)/If_led Part Type
Designator C7 C9 100nF
Part Type
Short Circuit
Application n2 : 20Hz to 20kHz bandwidth and 20dB gain BTL power amplifier. Components :
C9 Designator R1 R4 R6 R7* R8 C5 C6 C7 C9 C10 C12 S1, S2, S6, S7 S8 P1 D1* U1 Part Type C10 110k / 0.125W 22k / 0.125W Short Cicuit (Vcc-Vf_led)/If_led 10k / 0.125W P1 470nF D1* 100F U1 100nF Short Circuit Short Circuit 1F 2mm insulated Plug 10.16mm pitch 3 pts connector 2.54mm pitch PCB Phono Jack Led 3mm TS4890ID or TS4890IS S1, S2, S6, S7 S8 C12
Application n4 : Differential inputs BTL power amplifier. In this configuration, we need to place these components : R1, R4, R5, R6, R7, C4, C5, C12. We have also : R4 = R5, R1 = R6, C4 = C5. The gain of the amplifier is : GVDIFF = 2 R1 (Pos. Input - Neg. Input ) R4
For a 20Hz to 20kHz bandwidth and 6dB gain BTL power amplifier you could follow the bill of material below.
27/31
TS4890
Components :
Designator R1 R4 R5 R6 R7* R8 C4 C5 C6 C7 C9 C10 C12 D1* S1, S2, S6, S7 S8 P1, P2 U1 Part Type 22k / 0.125W 22k / 0.125W 22k / 0.125W 22k / 0.125W (Vcc-Vf_led)/If_led 10k / 0.125W 470nF 470nF 100F 100nF
-40
PSRR (dB)
In reality we want a value about -70dB. So, we need a gain of 34dB ! Now, on fig. 15 we can see the effect of Cb on the PSRR (input grounded) vs. frequency. With Cb=100F, we can reach the -70dB value. The process to obtain the final curve (Cb=100F, Cin=100nF, Rin=Rfeed=22k) is a simple transfer point by point on each frequency of the curve on fig. 16 to the curve on fig. 15. The measurement result is shown on the next figure. Fig. 105 : PSRR changes with Cb
-30 Cin=100nF Cb=1F
Vcc = 5 to 2.2V Rfeed = 22k, Rin = 22k Rg = 100, RL = 8 Tamb = 25C
Short Circuit Short Circuit 1F Led 3mm 2mm insulated Plug 10.16mm pitch 3 pts connector 2.54mm pitch PCB Phono Jack TS4890ID or TS4890IS
-50 -60 -70 10 100 1000
Frequency (Hz)
Cin=100nF Cb=100F
10000
100000
s Note on how to use the PSRR curves
(page 8) We have finished a design and we have chosen for the components : * Rin=Rfeed=22k * Cin=100nF * Cb=1F Now, on fig. 16, we can see the PSRR (input grounded) vs frequency curves. At 217Hz, we have a PSRR value of -36dB.
28/31
TS4890 s Note on PSRR measurement
What is the PSRR ?
The PSRR is the Power Supply Rejection Ratio. It's a kind of SVR in a determined frequency range. The PSRR of a device, is the ratio between a power supply disturbance and the result on the output. We can say that the PSRR is the ability of a device to minimize the impact of power supply disturbances to the output.
s Principle of operation
* We fixed the DC voltage supply (Vcc) * We fixed the AC sinusoidal ripple voltage (Vripple) * No bypass capacitor Cs is used The PSRR value for each frequency is : Rms (Vripple ) PSRR(dB) = 20 x Log10 Rms (Vs + - Vs - ) Remark : The measure of the Rms voltage is not a Rms selective measure but a full range (2 Hz to 125 kHz) Rms measure. It means that we measure the effective Rms signal + the noise.
How we measure the PSRR ?
Fig. 106 : PSRR measurement schematic
Rfeed Vripple Vcc 4 Rin Cin 2 Rg 100 Ohms 1 Bypass Standby Bias GND TS4890 Av=-1 + 8 Vs+ 3 VinVin+ + RL Vout2 6 Vcc
Vout1 5
Vs-
Cb
7
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TS4890
PACKAGE MECHANICAL DATA 8 PINS - PLASTIC MICROPACKAGE (SO)
L C a3 b1 c1
a2 b e3
A
s E
D M
8
5 F
1
4
Millimeters Dim. Min. A a1 a2 a3 b b1 C c1 D E e e3 F L M S 0.1 0.65 0.35 0.19 0.25 4.8 5.8 1.27 3.81 3.8 0.4 4.0 1.27 0.6 8 (max.) 0.150 0.016 Typ. Max. 1.75 0.25 1.65 0.85 0.48 0.25 0.5 45 (typ.) 5.0 6.2 0.189 0.228 Min. 0.004 0.026 0.014 0.007 0.010
a1
Inches Typ. Max. 0.069 0.010 0.065 0.033 0.019 0.010 0.020 0.197 0.244 0.050 0.150 0.157 0.050 0.024
30/31
TS4890
PACKAGE MECHANICAL DATA 8 PINS - PLASTIC MICROPACKAGE (miniSO)
k
0,25mm .010inch GAGEPLANE
c
L E1
SEATING PLANE
A A2 A1
5
C
E
4
D
L1 b
C
8 1
Dim. Min. A A1 A2 b c D E E1 e L L1 k aaa 0.050 0.780 0.250 0.130 2.900 4.750 2.900 0.400 0d
Millimeters Typ. 0.100 0.860 0.330 0.180 3.000 4.900 3.000 0.650 0.550 0.950 3d Max. 1.100 0.150 0.940 0.400 0.230 3.100 5.050 3.100 0.700 6d 0.100 Min. 0.002 0.031 0.010 0.005 0.114 0.187 0.114 0.016 0d
ccc
PIN1IDENTIFICA TION
e
Inches Typ. 0.004 0.034 0.013 0.007 0.118 0.193 0.118 0.026 0.022 0.037 3d Max. 0.043 0.006 0.037 0.016 0.009 0.122 0.199 0.122 0.028 6d 0.004
Information furni shed is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the consequences of use of such information nor for any infringe ment of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications mentioned in this publication are subject to change without notice. This publ ication supersedes and replaces all infor mation previously suppl ied. STMicroelectronics products are not authorized for use as critical compon ents in life support devices or systems without express written approval of STMicroelectronics. (c) The ST logo is a registered trademark of STMicroelectronics (c) 2001 STMicroelectronics - Printed in Italy - All Right s Reserved STMicroelectronics GROUP OF COMPANIES Australia - Brazil - Canada - China - Finland - France - Germany - Hong Kong - India - Israel - Italy - Japan - Malaysia Malta - Morocco - Singapore - Spain - Sweden - Swit zerland - United Kingdom - United States (c) http://w ww.st.com
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Price & Availability of TS4890IS

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