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LT1028/LT1128 Ultra Low Noise Precision High Speed Op Amps
FEATURES
s
DESCRIPTIO
s s
s
s s s s
Voltage Noise 1.1nV/Hz Max. at 1kHz 0.85nV/Hz Typ. at 1kHz 1.0nV/Hz Typ. at 10Hz 35nVP-P Typ., 0.1Hz to 10Hz Voltage and Current Noise 100% Tested Gain-Bandwidth Product LT1028: 50MHz Min. LT1128: 13MHz Min. Slew Rate LT1028: 11V/s Min. LT1128: 5V/s Min. Offset Voltage: 40V Max. Drift with Temperature: 0.8V/C Max. Voltage Gain: 7 Million Min. Available in 8-Pin SO Package
The LT1028(gain of -1 stable)/LT1128(gain of +1 stable) achieve a new standard of excellence in noise performance with 0.85nV/Hz 1kHz noise, 1.0nV/Hz 10Hz noise. This ultra low noise is combined with excellent high speed specifications (gain-bandwidth product is 75MHz for LT1028, 20MHz for LT1128), distortion-free output, and true precision parameters (0.1V/C drift, 10V offset voltage, 30 million voltage gain). Although the LT1028/ LT1128 input stage operates at nearly 1mA of collector current to achieve low voltage noise, input bias current is only 25nA. The LT1028/LT1128's voltage noise is less than the noise of a 50 resistor. Therefore, even in very low source impedance transducer or audio amplifier applications, the LT1028/LT1128's contribution to total system noise will be negligible.
APPLICATI
s s s s s s s
S
Low Noise Frequency Synthesizers High Quality Audio Infrared Detectors Accelerometer and Gyro Amplifiers 350 Bridge Signal Conditioning Magnetic Search Coil Amplifiers Hydrophone Amplfiers
Flux Gate Amplifier
10
VOLTAGE NOISE DENSITY (nV/Hz) DEMODULATOR SYNC OUTPUT TO DEMODULATOR 1k
+
LT1028
-
SQUARE WAVE DRIVE 1kHz FLUX GATE TYPICAL SCHONSTEDT #203132
1 1/f CORNER = 3.5Hz
50
0.1 0.1
1028/1128 TA01
U
Voltage Noise vs Frequency
VS = 15V TA = 25C MAXIMUM 1/f CORNER = 14Hz TYPICAL 1 10 100 FREQUENCY (Hz) 1k
1028/1128 TA02
UO
1
LT1028/LT1128 ABSOLUTE AXI U RATI GS
Operating Temperature Range LT1028/LT1128AM, M ..................... - 55C to 125C LT1028/LT1128AC, C ......................... - 40C to 85C Storage Temperature Range All Devices ........................................ - 65C to 150C Lead Temperature (Soldering, 10 sec.)................. 300C
Supply Voltage -55C to 105C ................................................ 22V 105C to 125C ................................................ 16V Differential Input Current (Note 8) ...................... 25mA Input Voltage ............................ Equal to Supply Voltage Output Short Circuit Duration .......................... Indefinite
PACKAGE/ORDER I FOR ATIO
TOP VIEW VOS TRIM 8 VOS TRIM 1
-
ORDER PART NUMBER
7 V+ 6 OUT 5 OVERCOMP
-IN 2
+
+IN 3 4 V- (CASE)
LT1028AMH LT1028MH LT1028ACH LT1028CH
H PACKAGE 8-LEAD TO-5 METAL CAN
TOP VIEW VOS TRIM 1 -IN 2 +IN 3 V
-
8
- +
VOS TRIM 7 V+ OUT
6
4
5 OVERCOMP
J8 PACKAGE 8-LEAD CERAMIC DIP N8 PACKAGE 8-LEAD PLASTIC DIP
LT1028AMJ8 LT1028MJ8 LT1028ACJ8 LT1028CJ8 LT1028ACN8 LT1028CN8 LT1128AMJ8 LT1128MJ8 LT1128CJ8 LT1128ACN8 LT1128CN8
ELECTRICAL CHARACTERISTICS
SYMBOL VOS VOS Time IOS IB en PARAMETER Input Offset Voltage Long Term Input Offset Voltage Stability Input Offset Current Input Bias Current Input Noise Voltage CONDITIONS (Note 1) (Note 2)
VS = 15V, TA = 25C, unless otherwise noted. LT1028AM/AC LT1128AM/AC
MIN TYP 10 0.3 12 25 35 MAX 40
VCM = 0V VCM = 0V 0.1Hz to 10Hz (Note 3)
2
U
U
W
WW
U
W
TOP VIEW VOS TRIM 1 -IN 2 +IN 3 V
-
ORDER PART NUMBER
8 7 6 5 VOS TRIM V+ OUT OVERCOMP
- +
LT1028CS8 LT1128CS8 S8 PART MARKING 1028 1128 ORDER PART NUMBER LT1028CS16
4
S8 PACKAGE 8-LEAD PLASTIC SOIC
TOP VIEW NC 1 NC 2 TRIM 3 -IN 4 +IN 5 V- 6 NC 7 NC 8
- +
16 NC 15 NC 14 TRIM 13 V + 12 OUT 11 OVERCOMP 10 NC 9 S PACKAGE 16-LEAD PLASTIC SOL NC
NOTE: THIS DEVICE IS NOT RECOMMENDED FOR NEW DESIGNS
LT1028M/C LT1128M/C
MIN TYP 20 0.3 18 30 35 MAX 80 UNITS V V/Mo nA nA nVP-P
50 90 75
100 180 90
LT1028/LT1128
ELECTRICAL CHARACTERISTICS
SYMBOL PARAMETER Input Noise Voltage Density In Input Noise Current Density Input Resistance Common Mode Differential Mode Input Capacitance Input Voltage Range Common-Mode Rejection Ratio Power Supply Rejection Ratio Large-Signal Voltage Gain
VS = 15V, TA = 25C, unless otherwise noted. LT1028AM/AC LT1128AM/AC LT1028M/C LT1128M/C
MIN TYP 1.0 0.9 4.7 1.0 300 20 5 12.2 126 132 30.0 20.0 15.0 13.0 12.2 15.0 6.0 75 20 80 7.6 MAX 1.9 1.2 12.0 1.8 UNITS nV/Hz nV/Hz pA/Hz pA/Hz M k pF V dB dB V/V V/V V/V V V V/s V/s MHz MHz mA
CONDITIONS fO = 10Hz (Note 4) fO = 1000Hz, 100% tested fO = 10Hz (Note 3 and 5) fO = 1000Hz, 100% tested
MIN
TYP 1.00 0.85 4.7 1.0
MAX 1.7 1.1 10.0 1.6
CMRR PSRR AVOL
VOUT SR GBW ZO IS
Maximum Output Voltage Swing Slew Rate Gain-Bandwidth Product Open-Loop Output Impedance Supply Current
VCM = 11V VS = 4V to 18V RL 2k, VO = 12V RL 1k, VO = 10V RL 600, VO = 10V RL 2k RL 600 AVCL = -1 AVCL = -1 fO = 20kHz (Note 6) fO = 200kHz (Note 6) VO = 0, IO = 0
LT1028 LT1128 LT1028 LT1128
300 20 5 11.0 12.2 114 126 117 133 7.0 30.0 5.0 20.0 3.0 15.0 12.3 13.0 11.0 12.2 11.0 15.0 5.0 6.0 50 75 13 20 80 7.4
11.0 110 110 5.0 3.5 2.0 12.0 10.5 11.0 4.5 50 11 9.5
10.5
ELECTRICAL CHARACTERISTICS
SYMBOL VOS VOS Temp IOS IB CMRR PSRR AVOL VOUT IS PARAMETER Input Offset Voltage Average Input Offset Drift Input Offset Current Input Bias Current Input Voltage Range Common-Mode Rejection Ratio Power Supply Rejection Ratio Large-Signal Voltage Gain Maximum Output Voltage Swing Supply Current CONDITIONS (Note 1) (Note7) VCM = 0V VCM = 0V
VS = 15V, -55C TA 125C, unless otherwise noted. LT1028AM LT1128AM
MIN
q q q q q q q q q q
LT1028M LT1128M
MAX 120 0.8 MIN TYP 45 0.25 30 50 11.7 120 130 14.0 10.0 11.6 9.0 MAX 180 1.0 180 300 UNITS V V/C nA nA V dB dB V/V V/V V mA
TYP 30 0.2
VCM = 10.3V VS = 4.5V to 16V RL 2k, VO = 10V RL 1k, VO = 10V RL 2k
25 40 10.3 11.7 106 122 110 130 3.0 14.0 2.0 10.0 10.3 11.6 8.7
90 150 10.3 100 104 2.0 1.5 10.3 11.5
13.0
3
LT1028/LT1128
ELECTRICAL CHARACTERISTICS
SYMBOL VOS V OS Temp IOS IB CMRR PSRR AVOL VOUT IS PARAMETER Input Offset Voltage Average Input Offset Drift Input Offset Current Input Bias Current Input Voltage Range Common-Mode Rejection Ratio Power Supply Rejection Ratio Large-Signal Voltage Gain Maximum Output Voltage Swing Supply Current CONDITIONS (Note 1) (Note7) VCM = 0V VCM = 0V
VS = 15V, 0C TA 70C, unless otherwise noted. LT1028AC LT1128AC
MIN
q q q q q q q q q q
LT1028C LT1128C
MAX 80 0.8 65 120 10.5 106 107 3.0 2.5 11.5 9.0 10.5 MIN TYP 30 0.2 22 40 12.0 124 132 25.0 18.0 12.7 10.5 8.2 MAX 125 1.0 130 240 UNITS V V/C nA nA V dB dB V/V V/V V V mA
TYP 15 0.1
VCM = 10.5V VS = 4.5V to 18V RL 2k, VO = 10V RL 1k, VO = 10V RL 2k RL 600 (Note 9)
15 30 10.5 12.0 110 124 114 132 5.0 25.0 4.0 18.0 11.5 12.7 9.5 11.0 8.0
11.5
ELECTRICAL CHARACTERISTICS
SYMBOL VOS V OS Temp IOS IB CMRR PSRR AVOL VOUT IS PARAMETER Input Offset Voltage Average Input Offset Drift Input Offset Current Input Bias Current Input Voltage Range Common-Mode Rejection Ratio Power Supply Rejection Ratio Large-Signal Voltage Gain Maximum Output Voltage Swing Supply Current CONDITIONS
VS = 15V, - 40C TA 85C, unless otherwise noted. (Note 10) LT1028AC LT1128AC
MIN
q q
LT1028C LT1128C
MAX 95 0.8 80 140 10.4 102 106 2.5 2.0 11.0 11.0 MIN TYP 35 0.25 28 45 11.8 123 131 20.0 14.0 12.5 8.7 MAX 150 1.0 160 280 UNITS V V/C nA nA V dB dB V/V V/V V mA
TYP 20 0.2
VCM = 0V VCM = 0V VCM = 10.5V VS = 4.5V to 18V RL 2k, VO = 10V RL 1k, VO = 10V RL 2k
q q q q q q q q
20 35 10.4 11.8 108 123 112 131 4.0 20.0 3.0 14.0 11.0 12.5 8.5
12.5
The q denotes specifications which apply over the full operating temperature range. Note 1: Input Offset Voltage measurements are performed by automatic test equipment approximately 0.5 sec. after application of power. In addition, at TA = 25C, offset voltage is measured with the chip heated to approximately 55C to account for the chip temperature rise when the device is fully warmed up. Note 2: Long Term Input Offset Voltage Stability refers to the average trend line of Offset Voltage vs. Time over extended periods after the first 30 days of operation. Excluding the initial hour of operation, changes in VOS during the first 30 days are typically 2.5V. Note 3: This parameter is tested on a sample basis only. Note 4: 10Hz noise voltage density is sample tested on every lot with the exception of the S8 and S16 packages. Devices 100% tested at 10Hz are available on request. Note 5: Current noise is defined and measured with balanced source resistors. The resultant voltage noise (after subtracting the resistor noise
on an RMS basis) is divided by the sum of the two source resistors to obtain current noise. Maximum 10Hz current noise can be inferred from 100% testing at 1kHz. Note 6: Gain-bandwidth product is not tested. It is guaranteed by design and by inference from the slew rate measurement. Note 7: This parameter is not 100% tested. Note 8: The inputs are protected by back-to-back diodes. Current-limiting resistors are not used in order to achieve low noise. If differential input voltage exceeds 1.8V, the input current should be limited to 25mA. Note 9: This parameter guaranteed by design, fully warmed up at TA = 70C. It includes chip temperature increase due to supply and load currents. Note 10: The LT1028/LT1128 are not tested and are not qualityassurance-sampled at -40C and at 85C. These specifications are guaranteed by design, correlation and/or inference from -55C, 0C, 25C, 70C and /or 125C tests.
4
LT1028/LT1128
TYPICAL PERFOR A CE CHARACTERISTICS
10Hz Voltage Noise Distribution
180 160 140
158 148
120 100 80 60 40 20 0 0.6
8 70 57
RMS VOLTAGE NOISE (V)
NUMBER OF UNITS
VS = 15V TA = 25C 500 UNITS MEASURED FROM 4 RUNS
28 74 3 2 2 2 12 3 21 1 1
0.8 1.0 1.2 1.4 1.6 1.8 2.0 VOLTAGE NOISE DENSITY (nV/Hz)
LT1020/1120 * TPC01
Total Noise vs Matched Source Resistance
100
RS
TOTAL NOISE DENSITY (nV/Hz)
RS
+
TOTAL NOISE DENSITY (nV/Hz)
-
CURRENT NOISE DENSITY (pA/Hz)
10 AT 10Hz 1 2 RS NOISE ONLY VS = 15V TA = 25C 0.1 1 3 10 30 100 300 1k 3k MATCHED SOURCE RESISTANCE () 10k AT 1kHz
LT1028/1128 * TPC04
0.1Hz to 10Hz Voltage Noise
VS = 15V TA = 25C
RMS VOLTAGE DENSITY (nV/Hz)
10nV
0
2
6 4 TIME (SEC)
LT1028/1128 * TPC07
UW
2.2 8 10
Wideband Noise, DC to 20kHz
10
Wideband Voltage Noise (0.1Hz to Frequency Indicated)
VS = 15V TA = 25C
1
0.1
VERTICAL SCALE = 0.5V/DIV HORIZONTAL SCALE = 0.5ms/DIV
0.01 100 1k 10k 100k BANDWIDTH (Hz) 1M 10M
LT1028/1128 * TPC03
Total Noise vs Unmatched Source Resistance
100
RS
Current Noise Spectrum
100
10
10
MAXIMUM 1/f CORNER = 800Hz TYPICAL
AT 10Hz 1
AT 1kHz
1 1/f CORNER = 250Hz
2 RS NOISE ONLY VS = 15V TA = 25C 0.1 1 3 10 30 100 300 1k 3k 10k UNMATCHED SOURCE RESISTANCE ()
LT1028/1128 * TPC05
0.1 10 100 1k FREQUENCY (Hz) 10k
LT1028/1128 * TPC06
0.01Hz to 1Hz Voltage Noise
2.0 VS = 15V TA = 25C
Voltage Noise vs Temperature
VS = 15V 1.6
1.2 AT 10Hz 0.8 AT 1kHz
10nV
O.4
0
20
60 40 TIME (SEC)
80
100
0 -50 -25
50 25 0 75 TEMPERATURE (C)
100
125
LT1028/1128 * TPC07
LT1028/1128 * TPC09
5
LT1028/LT1128
TYPICAL PERFOR A CE CHARACTERISTICS
20 18 16 14
UNITS (%)
Distribution of Input Offset Voltage
VS = 15V TA = 25C 800 UNITS TESTED FROM FOUR RUNS
30
OFFSET VOLTAGE CHANGE (V)
OFFSET VOLTAGE (V)
12 10 8 6 4 2 0 -50 -40 -30 -20 -10 0 10 20 30 40 50 OFFSET VOLTAGE (V)
LT1028/1128 * TPC10
Warm-Up Drift
24
INPUT BIAS AND OFFSET CURRENTS (nA)
CHANGE IN OFFSET VOLTAGE (V)
20 16
VS = 15V TA = 25C
INPUT BIAS CURRENT (nA)
METAL CAN (H) PACKAGE 12 8 4 0 0 1 2 3 4 TIME AFTER POWER ON (MINUTES) 5 DUAL-IN-LINE PACKAGE PLASTIC (N) OR CERDIP (J)
LT1028/1128 * TPC13
Voltage Noise vs Supply Voltage
1.5
RMS VOLTAGE NOISE DENSITY (nV/Hz) 10
TA = 25C 1.25
8
VS = 15V
SHORT-CIRCUIT CURRENT (mA) SINKING SOURCING
SUPPLY CURRENT (mA)
1.0
AT 10Hz AT 1kHz
0.75
0.5
0
5 10 15 SUPPLY VOLTAGE (V)
LT1028/1128 * TPC16
6
UW
Offset Voltage Drift with Temperature of Representative Units
50 40 VS = 15V
Long-Term Stability of Five Representative Units
10 8 6 4 2 0 -2 -4 -6 -8 VS = 15V TA = 25C t = 0 AFTER 1 DAY PRE-WARM UP
20 10 0 -10 -20 -30 -40 -50 -50 -25 50 25 0 75 TEMPERATURE (C) 100 125
-10
0
1
3 2 TIME (MONTHS)
4
5
LT1028/1128 * TPC11
LT1028/1128 * TPC12
Input Bias and Offset Currents Over Temperature
60 50 40 30 BIAS CURRENT 20 10 0 -50 -25 OFFSET CURRENT VS = 15V VCM = 0V
100 80 60 40 20 0 -20 -40 -60
Bias Current Over the CommonMode Range
RCM = 20V 300M VS = 15V 65nA TA = 25C POSITIVE INPUT CURRENT (UNDERCANCELLED) DEVICE
NEGATIVE INPUT CURRENT (OVERCANCELLED) DEVICE 10 5 -10 0 -5 COMMON-MODE INPUT VOLTAGE (V) 15
50 25 75 0 TEMPERATURE (C)
100
125
-80 -15
LT1028/1128 * TPC14
LT1028/1128 * TPC15
Supply Current vs Temperature
50 40 30 20 10 0 -10 -20 -30 -40
50 25 0 75 TEMPERATURE (C) 100 125 9
Output Short-Circuit Current vs Time
-50C 25C 125C VS = 15V
7 6 5 4 3 2 1 VS = 5V
125C 25C -50C
20
0 -50 -25
-50 3 2 0 1 TIME FROM OUTPUT SHORT TO GROUND (MINUTES)
LT1028/1128 * TPC18
LT1028/1128 * TPC17
LT1028/LT1128
TYPICAL PERFOR A CE CHARACTERISTICS
Voltage Gain vs Frequency
160 140 120
VOLTAGE GAIN (dB)
PHASE MARGIN (DEGREES)
OVERSHOOT (%)
LT1128 80 60 40 20 0 -20 0.01 0.1 1
LT1028
40 30 GAIN 20 10 0 VS = 15V TA = 25C CL = 10pF 100k 1M 10M FREQUENCY (Hz)
40 30 20 10 0 -10 100M
50 40 30 20 10 0 10
AV = -1, RS = 2k AV = -10 RS = 200 AV = -100 RS = 20 VS = 15V TA = 25C 10000
10 100 1k 10k 100k 1M 10M 100M FREQUENCY (Hz)
LT1028/1128 * TPC19
-10 10k
LT1028/1128 * TPC20
Gain Error vs Frequency Closed-Loop Gain = 1000
1 TYPICAL PRECISION OP AMP 0.1
VOLTAGE GAIN (dB) GAIN ERROR (%)
70 60
LT1128 Gain Phase vs Frequency
70 60 80 70
LT1128 Capacitance Load Handling
30pF 2k
PHASE MARGIN (DEGREES)
PHASE
LT1128
OVERSHOOT (%)
40 30 20 GAIN 10
40 30 20 10 VS = 15V TA = 25C CL = 10pF 100k 1M 10M FREQUENCY (Hz) 0 -10 100M
50 40 30 20 10 0 10
AV = -1, RS = 2k AV = -10 RS = 200 VS = 15V TA = 25C VO = 10mVP-P 10000
LT1028 0.01
0.001 0.1
GAIN ERROR = CLOSED-LOOP GAIN OPEN-LOOP GAIN 10 1 FREQUENCY (Hz) 100
LT1028/1128 * TPC22
0
-10 10k
AV = -100, RS = 20
LT1028/1128 * TPC23
Voltage Gain vs Supply Voltage
100
100
Voltage Gain vs Load Resistance
30
PEAK-TO-PEAK OUTPUT VOLTAGE (V)
VS = 15V
Maximum Undistorted Output vs Frequency
VS = 15V TA = 25C RL = 2k
TA = 25C
25 20 15 LT1128 10 5 LT1028
VOLTAGE GAIN (V/V)
VOLTAGE GAIN (V/V)
RL = 2k
TA = -55C 10
TA = 25C TA = 125C
10
RL = 600
ILMAX = 35mA AT -55C = 27mA AT 25C = 16mA AT 125C
1 0 5 10 15 SUPPLY VOLTAGE (V) 20
1 0.1
1 LOAD RESISTANCE (k)
10
10k
LT1028/1128 * TPC25
LT1028/1128 * TPC26
+
-
50
50
60
RS
+
100
VOLTAGE GAIN (dB)
-
VS = 15V TA = 25C RL = 2k
UW
LT1028 Gain, Phase vs Frequency
70 PHASE 60 50 60 50
70 60
LT1028 Capacitance Load Handling
70
80
30pF 2k RS
CL
100 1000 CAPACITIVE LOAD (pF)
LT1028/1128 * TPC21
CL
100 1000 CAPACITIVE LOAD (pF)
LT1028/1128 * TPC 24
100k 1M FREQUENCY (Hz)
10M
LT1028/1128 * TPC27
7
LT1028/LT1128
TYPICAL PERFOR A CE CHARACTERISTICS
LT1028 Large-Signal Transient Response
50mV 20mV/DIV
10V 5V/DIV
SLEW RATE (V/s)
-10V -50mV
1s/DIV AV = -1, RS = RF = 2k, C F = 15pF
LT1128 Large-Signal Transient Response
50mV 10V
SLEW RATE (V/s)
0V
-10V -50mV
2s/DIV AV = -1, R S = RF = 2k, CF = 30pF
Closed-Loop Output Impedance
100 IO = 1mA VS = 15V TA = 25C AV = +1000 1 LT1128 LT1028
10 100
OUTPUT IMPEDANCE ()
10
100
SLEW RATE (V/s)
SLEW RATE (V/s)
0.1 LT1128 AV = +5 LT1028
0.01
0.001
10
100
10k 1k FREQUENCY (Hz)
100k
LT1028/1128 * TPC34
8
UW
1M
LT1028 Small-Signal Transient Response
18 17 16 15 14 13
LT1028 Slew Rate, Gain-Bandwidth Product Over Temperature
GAIN-BANDWIDTH PRODUCT (fO = 20kHz), (MHz)
VS = 15V GBW FALL RISE 90 80 70 60 50 40 30 125
0.2s/DIV AV = -1, RS = RF = 2k CF = 15pF, C L = 80pF
12 -50 -25
50 25 75 0 TEMPERATURE (C)
100
LT1028/1128 * TPC30
LT1128 Small-Signal Transient Response
9 8 7
LT1128 Slew Rate, Gain-Bandwidth Product Over Temperature
GAIN-BANDWIDTH PRODUCT (fO = 200kHz), (MHz)
FALL
RISE 6 5 4 3 2 10 GBW 20 30
0V
0.2s/DIV AV = +1, C L = 10pF
1 0 -50 -25 75 50 25 0 TEMPERATURE (C) 100 125
LT1028/1128 * TPC33
LT1128 Slew Rate, Gain-Bandwidth Product vs Over-Compensation Capacitor
1k
LT1028 Slew Rate, Gain-Bandwidth Product vs Over-Compensation Capacitor
100 10k
GBW SLEW RATE
SLEW 10
GAIN AT 200kHz
GBW 1k
GAIN AT 20kHz
1
10
1 COC FROM PIN 5 TO PIN 6 VS = 15V TA = 25C 0.1 1
100
0.1 1
1 100 1000 10000 10 OVER-COMPENSATION CAPACITOR (pF)
LT1028/1128 * TPC35
10 10 100 1000 10000 OVER-COMPENSATION CAPACITOR (pF)
LT1028/1128 * TPC36
LT1028/LT1128
TYPICAL PERFOR A CE CHARACTERISTICS
Common-Mode Limit Over Temperature
V+
COMMON-MODE REJECTION RATIO (dB)
POWER SUPPLY REJECTION RATIO (dB)
-1
COMMON-MODE LIMIT (V) REFERRED TO POWER SUPPLY
-2 -3 -4
VS = 5V VS = 15V
4 3 2 1 V- -50 -25 50 25 0 75 TEMPERATURE (C) 100 125 VS = 5V TO 15V
LT1028/1128 * TPC37
LT1028 Total Harmonic Distortion vs Frequency and Load Resistance
0.1
0.1
TOTAL HARMONIC DISTORTION (%)
AV = +1000 RL = 600
TOTAL HARMONIC DISTORTION (%)
0.01
NOISE VOLTAGE DENSITY (nV/Hz)
AV = +1000 RL = 2k
0.01
AV = -1000 RL = 2k AV = +1000 RL = 600 VO = 20VP-P VS = 15V TA = 25C 10 FREQUENCY (kHz) 100
LT1028/1128 * TPC40
0.001 1
LT1128 Total Harmonic Distortion vs Frequency and Load Resistance
1.0
TOTAL HARMONIC DISTORTION (%)
0.1
AV = +1000 RL = 2k
AV = +1000 RL = 600
TOTAL HARMONIC DISTORTION (%)
0.01
0.001 1.0
UW
Common-Mode Rejection Ratio vs Frequency
140 120 100 LT1128 80 60 40 20 0 10 100 100k 10k 1k FREQUENCY (Hz) 1M 10M LT1028 VS = 15V TA = 25C
Power Supply Rejection Ratio vs Frequency
160 140 120 100 80 60 40 20 0 0.1 1 10 100 1k 10k 100k 1M 10M FREQUENCY (Hz)
LT1028/1128 * TPC39
VS = 15V TA = 25C
NEGATIVE SUPPLY POSITIVE SUPPLY
LT1028/1128 * TPC38
LT1028 Total Harmonic Distortion vs Closed-Loop Gain
10
VO = 20VP-P f = 1kHz VS = 15V TA = 25C RL = 10k NON-INVERTING GAIN
High Frequency Voltage Noise vs Frequency
1.0
0.001
INVERTING GAIN MEASURED EXTRAPOLATED 10 100 1k 10k CLOSED LOOP GAIN 100k
0.0001
0.1 10k
100k FREQUENCY (Hz)
1M
LT1028/1128 * TPC42
LT1028/1128 * TPC41
LT1128 Total Harmonic Distortion vs Closed-Loop Gain
0.1 VO = 20VP-P f = 1kHz VS = 15V TA = 25C RL = 10k NON-INVERTING GAIN
0.01
AV = -1000 RL = 2k AV = +1000 RL = 600 VO = 20VP-P VS = 15V TA = 25C 10 FREQUENCY (kHz) 100
LT1028/1128 * TPC43
0.001
INVERTING GAIN
MEASURED EXTRAPOLATED 10 100 1k 10k CLOSED LOOP GAIN 100k
0.0001
LT1028/1128 * TPC44
9
LT1028/LT1128
APPLICATI S I FOR ATIO - OISE
largest term, as in the example above, and the LT1028/ LT1128's voltage noise becomes negligible. As Req is further increased, current noise becomes important. At 1kHz, when Req is in excess of 20k, the current noise component is larger than the resistor noise. The total noise versus matched source resistance plot illustrates the above calculations. The plot also shows that current noise is more dominant at low frequencies, such as 10Hz. This is because resistor noise is flat with frequency, while the 1/f corner of current noise is typically at 250Hz. At 10Hz when Req > 1k, the current noise term will exceed the resistor noise. When the source resistance is unmatched, the total noise versus unmatched source resistance plot should be consulted. Note that total noise is lower at source resistances below 1k because the resistor noise contribution is less. When RS > 1k total noise is not improved, however. This is because bias current cancellation is used to reduce input bias current. The cancellation circuitry injects two correlated current noise components into the two inputs. With matched source resistors the injected current noise creates a common-mode voltage noise and gets rejected by the amplifier. With source resistance in one input only, the cancellation noise is added to the amplifier's inherent noise. In summary, the LT1028/LT1128 are the optimum amplifiers for noise performance, provided that the source resistance is kept low. The following table depicts which op amp manufactured by Linear Technology should be used to minimize noise, as the source resistance is increased beyond the LT1028/LT1128's level of usefulness.
1028/1128 AI01
Voltage Noise vs Current Noise The LT1028/LT1128's less than 1nV/Hz voltage noise is three times better than the lowest voltage noise heretofore available (on the LT1007/1037). A necessary condition for such low voltage noise is operating the input transistors at nearly 1mA of collector currents, because voltage noise is inversely proportional to the square root of the collector current. Current noise, however, is directly proportional to the square root of the collector current. Consequently, the LT1028/LT1128's current noise is significantly higher than on most monolithic op amps. Therefore, to realize truly low noise performance it is important to understand the interaction between voltage noise (en), current noise (In) and resistor noise (rn). Total Noise vs Source Resistance The total input referred noise of an op amp is given by et = [en2 + rn2 + (InReq)2]1/2 where Req is the total equivalent source resistance at the two inputs, and rn = 4kTReq = 0.13Req in nV/Hz at 25C As a numerical example, consider the total noise at 1kHz of the gain 1000 amplifier shown below.
100 100k
-
100 LT1028 LT1128
+
Req = 100 + 100 || 100k 200 rn = 0.13200 = 1.84nVHz en = 0.85nVHz In = 1.0pA/Hz et = [0.852 + 1.842 + (1.0 x 0.2) 2]1/2 = 2.04nV/Hz Output noise = 1000 et = 2.04V/Hz At very low source resistance (Req < 40) voltage noise dominates. As Req is increased resistor noise becomes the
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Best Op Amp for Lowest Total Noise vs Source Resistance
SOURCE RESISTANCE() (Note 1) 0 to 400 400 to 4k 4k to 40k 40k to 500k 500k to 5M >5M BEST OP AMP AT LOW FREQ(10Hz) WIDEBAND(1kHz) LT1028/LT1128 LT1007/1037 LT1001 LT1012 LT1012 or LT1055 LT1055 LT1028/LT1128 LT1028/LT1128 LT1007/1037 LT1001 LT1012 LT1055
Note 1: Source resistance is defined as matched or unmatched, e.g., RS = 1k means: 1k at each input, or 1k at one input and zero at the other.
LT1028/LT1128
APPLICATI
S I FOR ATIO - OISE
Measuring the typical 35nV peak-to-peak noise performance of the LT1028/LT1128 requires special test precautions: (a) The device should be warmed up for at least five minutes. As the op amp warms up, its offset voltage changes typically 10V due to its chip temperature increasing 30C to 40C from the moment the power supplies are turned on. In the 10 second measurement interval these temperature-induced effects can easily exceed tens of nanovolts. (b) For similar reasons, the device must be well shielded from air current to eliminate the possibility of thermoelectric effects in excess of a few nanovolts, which would invalidate the measurements. (c) Sudden motion in the vicinity of the device can also "feedthrough" to increase the observed noise. A noise-voltage density test is recommended when measuring noise on a large number of units. A 10Hz noisevoltage density measurement will correlate well with a 0.1Hz to 10Hz peak-to-peak noise reading since both results are determined by the white noise and the location of the 1/f corner frequency.
Noise Testing - Voltage Noise The LT1028/LT1128's RMS voltage noise density can be accurately measured using the Quan Tech Noise Analyzer, Model 5173 or an equivalent noise tester. Care should be taken, however, to subtract the noise of the source resistor used. Prefabricated test cards for the Model 5173 set the device under test in a closed-loop gain of 31 with a 60 source resistor and a 1.8k feedback resistor. The noise of this resistor combination is 0.1358 = 1.0nV/Hz. An LT1028/LT1128 with 0.85nV/Hz noise will read (0.852 + 1.02)1/2 = 1.31nV/Hz. For better resolution, the resistors should be replaced with a 10 source and 300 feedback resistor. Even a 10 resistor will show an apparent noise which is 8% to 10% too high. The 0.1Hz to 10Hz peak-to-peak noise of the LT1028/ LT1128 is measured in the test circuit shown. The frequency response of this noise tester indicates that the 0.1Hz corner is defined by only one zero. The test time to measure 0.1Hz to 10Hz noise should not exceed 10 seconds, as this time limit acts as an additional zero to eliminate noise contributions from the frequency band below 0.1Hz.
0.1Hz to 10Hz Noise Test Circuit
0.1F 100k
GAIN (dB)
-
100
2k
*
+
LT1001
+
4.7F
-
100k VOLTAGE GAIN = 50,000 * DEVICE UNDER TEST NOTE ALL CAPACITOR VALUES ARE FOR NONPOLARIZED CAPACITORS ONLY 24.3k 0.1F
2.2F
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0.1Hz to 10Hz Peak-to-Peak Noise Tester Frequency Response
100 90 80 22F 70 60 50 40 30 0.01
1028/1128 AI02
SCOPE x1 RIN = 1M 110k
0.1
1.0 10 FREQUENCY (Hz)
100
LT1028/1128 * AI03
11
LT1028/LT1128
APPLICATI S I FOR ATIO - OISE
10Hz voltage noise density is sample tested on every lot. Devices 100% tested at 10Hz are available on request for an additional charge. 10Hz current noise is not tested on every lot but it can be inferred from 100% testing at 1kHz. A look at the current noise spectrum plot will substantiate this statement. The only way 10Hz current noise can exceed the guaranteed limits is if its 1/f corner is higher than 800Hz and/or its white noise is high. If that is the case then the 1kHz test will fail.
eno
Noise Testing - Current Noise Current noise density (In) is defined by the following formula, and can be measured in the circuit shown:
In =
[eno - (31 x 18.4nV/Hz) ] 20k x 31
2
1.8k 10k 60
2 1/2
-
LT1028 LT1128
10k
+
1028/1128 AI04
NOISE FILTER LOSS (dB)
If the Quan Tech Model 5173 is used, the noise reading is input-referred, therefore the result should not be divided by 31; the resistor noise should not be multiplied by 31. 100% Noise Testing The 1kHz voltage and current noise is 100% tested on the LT1028/LT1128 as part of automated testing; the approximate frequency response of the filters is shown. The limits on the automated testing are established by extensive correlation tests on units measured with the Quan Tech Model 5173.
APPLICATI
General
S I FOR ATIO
The LT1028/LT1128 series devices may be inserted directly into OP-07, OP-27, OP-37, LT1007 and LT1037 sockets with or without removal of external nulling components. In addition, the LT1028/LT1128 may be fitted to 5534 sockets with the removal of external compensation components. Offset Voltage Adjustment The input offset voltage of the LT1028/LT1128 and its drift with temperature, are permanently trimmed at wafer testing to a low level. However, if further adjustment of VOS is necessary, the use of a 1k nulling potentiometer will not degrade drift with temperature. Trimming to a value other
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Automated Tester Noise Filter
10 0 -10 -20 -30 -40 -50 100 CURRENT NOISE VOLTAGE NOISE
1k
10k
100k
LT1028/1128 * AI05
FREQUENCY (Hz)
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1k 15V 1 2 INPUT 3
- +
8 76 OUTPUT
LT1028 LT1128 4 -15V
1028/1128 AI06
than zero creates a drift of (VOS/300)V/C, e.g., if VOS is adjusted to 300V, the change in drift will be 1V/C. The adjustment range with a 1k pot is approximately 1.1mV. Offset Voltage and Drift Thermocouple effects, caused by temperature gradients across dissimilar metals at the contacts to the input
LT1028/LT1128
APPLICATI S I FOR ATIO U
Frequency Response The LT1028's Gain, Phase vs Frequency plot indicates that the device is stable in closed-loop gains greater than +2 or -1 because phase margin is about 50 at an open-loop gain of 6dB. In the voltage follower configuration phase margin seems inadequate. This is indeed true when the output is shorted to the inverting input and the noninverting input is driven from a 50 source impedance. However, when feedback is through a parallel R-C network (provided CF < 68pF), the LT1028 will be stable because of interaction between the input resistance and capacitance and the feedback network. Larger source resistance at the noninverting input has a similar effect. The following voltage follower configurations are stable:
33pF 2k
1028/1128 AI08
terminals, can exceed the inherent drift of the amplifier unless proper care is exercised. Air currents should be minimized, package leads should be short, the two input leads should be close together and maintained at the same temperature. The circuit shown to measure offset voltage is also used as the burn-in configuration for the LT1028/LT1128.
Test Circuit for Offset Voltage and Offset Voltage Drift with Temperature
10k* 15V 2 200* 3 10k*
- +
7 6 VO
LT1028 LT1128 4 -15V
VO = 100VOS * RESISTORS MUST HAVE LOW THERMOELECTRIC POTENTIAL
Unity-Gain Buffer Applications (LT1128 Only) When RF 100 and the input is driven with a fast, largesignal pulse (>1V), the output waveform will look as shown in the pulsed operation diagram.
RF
-
OUTPUT 6V/s
1028/1128 AI07
+
During the fast feedthrough-like portion of the output, the input protection diodes effectively short the output to the input and a current, limited only by the output short-circuit protection, will be drawn by the signal generator. With RF 500, the output is capable of handling the current requirements (IL 20mA at 10V) and the amplifier stays in its active mode and a smooth transition will occur. As with all operational amplifiers when RF > 2k, a pole will be created with RF and the amplifier's input capacitance, creating additional phase shift and reducing the phase margin. A small capacitor (20pF to 50pF) in parallel with RF will eliminate this problem.
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LT1028
-
500 LT1028
+
50
+
50
1028/1128 AI09
Another configuration which requires unity-gain stability is shown below. When CF is large enough to effectively short the output to the input at 15MHz, oscillations can occur. The insertion of RS2 500 will prevent the LT1028 from oscillating. When RS1 500, the additional noise contribution due to the presence of RS2 will be minimal. When RS1 100, RS2 is not necessary, because RS1 represents a heavy load on the output through the CF short. When 100 < RS1 < 500, RS2 should match RS1 . For example, RS1 = RS2 = 300 will be stable. The noise increase due to RS2 is 40%.
C1
R1 RS1
-
LT1028
RS2
+
1028/1128 AI10
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LT1028/LT1128
APPLICATI
S I FOR ATIO
If CF is only used to cut noise bandwidth, a similar effect can be achieved using the over-compensation terminal. The Gain, Phase plot also shows that phase margin is about 45 at gain of 10 (20dB). The following configura10pF
10k 1.1k
-
LT1028
+
50
1028/1128 AI11
TYPICAL APPLICATI
Strain Gauge Signal Conditioner with Bridge Excitation
15V 3 5.0V 2
LT1021-5
+ -
7 6
330
LT1128 4 -15V 350 BRIDGE
REFERENCE OUTPUT 15V 3 301k* 7 6 1F
- +
LT1028 10k ZERO TRIM 2 4 -15V
15V 3
- +
7 6 330 *RN60C FILM RESISTORS
LT1028 2 4
-15V
THE LT1028's NOISE CONTRIBUTION IS NEGLIGIBLE COMPARED TO THE BRIDGE NOISE.
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tion has a high (70%) overshoot without the 10pF capacitor because of additional phase shift caused by the feedback resistor - input capacitance pole. The presence of the 10pF capacitor cancels this pole and reduces overshoot to 5%. Over-Compensation The LT1028/LT1128 are equipped with a frequency overcompensation terminal (pin 5). A capacitor connected between pin 5 and the output will reduce noise bandwidth. Details are shown on the Slew Rate, Gain-Bandwidth Product vs Over-Compensation Capacitor plot. An additional benefit is increased capacitive load handling capability.
Low Noise Voltage Regulator
28V + 121 LT317A 10 28V 1k LT1021-10 2.3k PROVIDES PRE-REG AND CURRENT LIMITING 10
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LT1028
330 2N6387
-
0V TO 10V OUTPUT 30.1k*
1000pF 2k
20V OUTPUT
5k GAIN TRIM
49.9*
2k
1028/1128 TA04
1028/1128 TA05
LT1028/LT1128
TYPICAL APPLICATI
Paralleling Amplifiers to Reduce Voltage Noise
10
+
A1 LT1028
1.5k
-
7.5 470
+
A2 LT1028
1.5k
-
7.5 470
+
An LT1028
1.5k
-
7.5 470
1.ASSUME VOLTAGE NOISE OF LT1028 AND 7.5 SOURCE RESISTOR = 0.9nV/Hz. 2.GAIN WITH n LT1028s IN PARALLEL = n x 200. 3.OUTPUT NOISE = n x 200 x 0.9nV/Hz. 0.9 4.INPUT REFERRED NOISE = OUTPUT NOISE = nV/ Hz. n x 200 n 5.NOISE CURRENT AT INPUT INCREASES n TIMES. 2V 6.IF n = 5, GAIN = 1000, BANDWIDTH = 1MHz, RMS NOISE, DC TO 1MHz = = 0.9 V. 5
Low Noise, Wide Bandwidth Instrumentation Amplifier
+
LT1028
-INPUT
300 820 68pF
-
50 10
-
LT1028 +INPUT
820
68pF 300
+
10k
100
1028/1128 TA09
GAIN = 1000, BANDWIDTH = 1MHz INPUT REFERRED NOISE = 1.5nV/Hz AT 1kHz WIDEBAND NOISE -DC to 1MHz = 3VRMS IF BW LIMITED TO DC TO 100kHz = 0.55VRMS
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Phono Preamplifier
787 15V 2 100pF
4.7k
0.1F 10k 0.33F 6 OUTPUT
- +
7 LT1028
3 47k
4 -15V ALL RESISTORS METAL FILM
-
LT1028 OUTPUT
+
MAG PHONO INPUT
1028/1128 TA06
Tape Head Amplifier
0.1F 499 31.6k 10 2
-
LT1028 6 OUTPUT
TAPE HEAD INPUT
3
+
1028/1128 TA07
1028/1128 TA03
ALL RESISTORS METAL FILM
Gyro Pick-Off Amplifier
10k
GYRO TYPICAL- NORTHROP CORP. GR-F5AH7-5B SINE DRIVE
-
LT1028 OUTPUT
*
+
LT1028 OUTPUT TO SYNC DEMODULATOR 1k
+
-
1028/1128 TA08
15
LT1028/LT1128
TYPICAL APPLICATI
C1 0.047 20 R1 2k
Super Low Distortion Variable Sine Wave Oscillator
C2 0.047
20 2k R2
+
LT1028
-
2.4k 5.6k 10pF 15F 22k
2N4338 560
100k LT1055 20k TRIM FOR LOWEST DISTORTION
<0.0018% DISTORTION AND NOISE. MEASUREMENT LIMITED BY RESOLUTION OF HP339A DISTORTION ANALYZER
5V
10
+
1k 33 100F SYNCHRONOUS DEMODULATOR 10k* OPTICAL CHOPPER WHEEL IR RADIATION PHOTOELECTRIC PICK-OFF 267 1000F 3 5V 5V 2 6 8 4 -5V INFRA RED ASSOCIATES, INC. HgCdTe IR DETECTOR 13 AT 77K 10 10k 14 16 1/4 LTC1043 13 12 3 7 LT1028 2 10k*
+
100F
+
39
16
-
10k
+
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Chopper-Stabilized Amplifier
15V 1N758 3
+ -
1
7 LT1052 6 8 4 0.1 0.01
1VRMS OUTPUT 1.5kHz TO 15kHz 1 f= 2RC WHERE R1C1 = R2C2 4.7k 15V
(
)
2
0.1
LT1004-1.2V
-15V 100k
1N758
15V
130 1 7
68
30k
+
MOUNT 1N4148s IN CLOSE PROXIMITY
INPUT
3
+
LT1028
8 OUTPUT 10k 4 -15V 10
2
-
10k
1028/1128 TA10
1028/1128 TA11
Low Noise Infrared Detector
+ -
+ -
4 -5V
7 6 8 1M 3 30pF 2
5V
LM301A 1
+ -
4
7 LT1012 1 -5V 6 8 DC OUT
1028/1128 TA12
LT1028/LT1128
SCHE ATIC DIAGRA
NULL 8 R5 130 R6 130
NULL 1
R1 3k
R2 3k
900A
900A
Q5 3 1 Q8 3
NONINVERTING INPUT 3 4.5A Q1
Q7 4.5A
4.5A 4.5A Q2
INTERVING INPUT 2
0 1.8mA BIAS Q3 300A Q15 Q21 R7 80 R8 480 600A Q20 Q23
V- 4 C2 = 50pF for LT1028 C2 = 275pF for LT1128 5 OVERCOMP
1028/1128 TA13
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V+ 7 Q4 C1 257pF 500A Q17 Q16 Q18 R10 400 R11 400 Q19 R10 C2 500 Q26 Q6 1 Q11 Q9 R11 100 C3 250pF Q24 1.5A Q12 Q13 1.5A Q14 R12 240 C4 35pF Q27 Q25 OUTPUT 6 Q22 1.1mA 2.3mA 400A Q10
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LT1028/LT1128
PACKAGE DESCRIPTIO U
Dimensions in inches (millimeters) unless otherwise noted. J8 Package 8-Lead Ceramic DIP
0.290 - 0.320 (7.366 - 8.128) 0.200 (5.080) MAX 0.015 - 0.060 (0.381 - 1.524) 0.005 (0.127) MIN
0.405 (10.287) MAX 8 7 6 5
0.008 - 0.018 (0.203 - 0.460) 0.385 0.025 (9.779 0.635)
0.025 (0.635) RAD TYP 1 2 3
0.220 - 0.310 (5.588 - 7.874)
0 - 15 4
0.038 - 0.068 (0.965 - 1.727) 0.014 - 0.026 (0.360 - 0.660)
0.125 3.175 0.100 0.010 MIN (2.540 0.254)
0.055 (1.397) MAX
TJMAX 165C
JA 100C/W
N8 Package 8-Lead Plastic DIP
0.300 - 0.320 (7.620 - 8.128) 0.045 - 0.065 (1.143 - 1.651) 0.130 0.005 (3.302 0.127) 0.400 (10.160) MAX 8 7 6 5
0.009 - 0.015 (0.229 - 0.381)
0.065 (1.651) TYP 0.125 (3.175) MIN 0.020 (0.508) MIN
0.250 0.010 (6.350 0.254)
(
+0.025 0.325 -0.015 +0.635 8.255 -0.381
)
0.045 0.015 (1.143 0.381) 0.100 0.010 (2.540 0.254)
1
2
3
4
0.018 0.003 (0.457 0.076)
TJMAX 130C
JA 130C/W
S8 Package 8-Lead Plastic SOIC
0.010 - 0.020 x 45 (0.254 - 0.508) 0.008 - 0.010 (0.203 - 0.254) 0.016 - 0.050 0.406 - 1.270 0.053 - 0.069 (1.346 - 1.752) 0.004 - 0.010 (0.101 - 0.254) 0.228 - 0.244 (5.791 - 6.197) 8
0.189 - 0.197 (4.801 - 5.004) 7 6 5
0- 8 TYP
0.014 - 0.019 (0.355 - 0.483)
0.050 (1.270) BSC
0.150 - 0.157 (3.810 - 3.988)
TJMAX 135C
JA 140C/W
1
2
3
4
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LT1028/LT1128
PACKAGE DESCRIPTIO
0.291 - 0.299 (7.391 - 7.595) 0.005 (0.127) RAD MIN
0.010 - 0.029 x 45 (0.254 - 0.737)
0.093 - 0.104 (2.362 - 2.642)
0 - 8 TYP
0.009 - 0.013 (0.229 - 0.330)
SEE NOTE 0.016 - 0.050 (0.406 - 1.270)
NOTE: PIN 1 IDENT, NOTCH ON TOP AND CAVITIES ON THE BOTTOM OF PACKAGES ARE THE MANUFACTURING OPTIONS. THE PART MAY BE SUPPLIED WITH OR WITHOUT ANY OF THE OPTIONS.
45TYP 0.027 - 0.034 (0.686 - 0.864) 7 6 5 0.110 - 0.160 (2.794 - 4.064) INSULATING STANDOFF 1
0.027 - 0.045 (0.686 - 1.143) 8 2 3 4 0.200 - 0.230 (5.080 - 5.842) BSC SEATING PLANE
NOTE: LEAD DIAMETER IS UNCONTROLLED BETWEEN THE REFERENCE PLANE AND SEATING PLANE.
Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
U
Dimensions in inches (millimeters) unless otherwise noted. S Package 16-Lead Plastic SOL
0.037 - 0.045 (0.940 - 1.143) 16 15
0.398 - 0.413 (10.109 - 10.490) 14 13 12 11 10 9
SEE NOTE 0.050 (1.270) TYP 0.004 - 0.012 (0.102 - 0.305)
0.394 - 0.419 (10.007 - 10.643)SOL16
0.014 - 0.019 (0.356 - 0.482) TYP
1
2
3
4
5
6
7
8
T JMAX 140C
JA 130C/W
H Package 8-Lead TO-5 Metal Can
0.335 - 0.370 (8.509 - 9.398) DIA 0.305 - 0.335 (7.747 - 8.509) 0.040 (1.016) MAX 0.050 (1.270) MAX GAUGE PLANE 0.165 - 0.185 (4.191 - 4.699) REFERENCE PLANE 0.500 - 0.750 (12.70 - 19.05)
0.010 - 0.045 (0.254 - 1.143) 0.016 - 0.021 (0.406 - 0.533) TYP
TJMAX 175C
JA
JC
140C/W 40C/W
19
LT1028/LT1128
U.S. Area Sales Offices
NORTHEAST REGION Linear Technology Corporation One Oxford Valley 2300 E. Lincoln Hwy.,Suite 306 Langhorne, PA 19047 Phone: (215) 757-8578 FAX: (215) 757-5631 SOUTHEAST REGION Linear Technology Corporation 17060 Dallas Parkway Suite 208 Dallas, TX 75248 Phone: (214) 733-3071 FAX: (214) 380-5138 CENTRAL REGION Linear Technology Corporation Chesapeake Square 229 Mitchell Court, Suite A-25 Addison, IL 60101 Phone: (708) 620-6910 FAX: (708) 620-6977 SOUTHWEST REGION Linear Technology Corporation 22141 Ventura Blvd. Suite 206 Woodland Hills, CA 91364 Phone: (818) 703-0835 FAX: (818) 703-0517 NORTHWEST REGION Linear Technology Corporation 782 Sycamore Dr. Milpitas, CA 95035 Phone: (408) 428-2050 FAX: (408) 432-6331
International Sales Offices
FRANCE Linear Technology S.A.R.L. Immeuble "Le Quartz" 58 Chemin de la Justice 92290 Chatenay Mallabry France Phone: 33-1-46316161 FAX: 33-1-46314613 GERMANY Linear Techonolgy GMBH Untere Hauptstr. 9 D-8057 Eching Germany Phone: 49-89-3197410 FAX: 49-89-3194821 JAPAN Linear Technology KK 4F Ichihashi Building 1-8-4 Kudankita Chiyoda-Ku Tokyo, 102 Japan Phone: 81-3-3237-7891 FAX: 81-3-3237-8010 KOREA Linear Technology Korea Branch Namsong Building, #505 Itaewon-Dong 260-199 Yongsan-Ku, Seoul Korea Phone: 82-2-792-1617 FAX: 82-2-792-1619 SINGAPORE Linear Technology Pte. Ltd. 101 Boon Keng Road #02-15 Kallang Ind. Estates Singapore 1233 Phone: 65-293-5322 FAX: 65-292-0398 TAIWAN Linear Technology Corporation Rm. 801, No. 46, Sec. 2 Chung Shan N. Rd. Taipei, Taiwan, R.O.C. Phone: 886-2-521-7575 FAX: 886-2-562-2285
UNITED KINGDOM Linear Technology (UK) Ltd. The Coliseum, Riverside Way Camberley, Surrey GU15 3YL United Kingdom Phone: 44-276-677676 FAX: 44-276-64851
World Headquarters
Linear Technology Corporation 1630 McCarthy Blvd. Milpitas, CA 95035-7487 Phone: (408) 432-1900 FAX: (408) 434-0507
07/10/92
20
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7487
(408) 432-1900 q FAX: (408) 434-0507 q TELEX: 499-3977
LT/GP 0792 10K REV 0
(c) LINEAR TECHNOLOGY CORPORATION 1992

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