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UTC2030
18W Hi-Fi AMPLIFIER AND 35W DRIVER
DESCRIPTION
LINEAR INTEGRATED CIRCUIT
The UTC2030 is a monolithic IC in Pentawatt package intended for use as low frequency class AB amplifier. With Vsmax=32V it is particularly suited for more reliable applications without regulated supply and for 35W driver circuits using lowcost complementary pairs. The UTC2030 provides high output current and has very low harmonic and cross-over distortion. Further the device incorporates a short circuit protection system comprising an arrangement for automatically limiting the dissipated power to as to keep the working point of the output transistors within their safe operating area. A conventional thermal shut-down system is also included.
TO-220B
ABSOLUTE MAXIMUM RATINGS(Ta=25C)
CHARACTERISTICS
Supply Voltage Input Voltage Differential input voltage Peak output current (internally limited) Total power dissipation at Tcase=90C Storage temperature junction temperature
SYMBOL
Vs Vi Vdi Io Ptot Tstg Tj
VALUE
20 Vs 13 3.5 20 -40~+150 -40~+150
UNITS
V V V A W
C C
TYPICAL APPLICATION
+Vs
C5 100nF C3 100F D1 1N4001
Vi
C1 1F
1
R3 22k
5 UTC2030 3
R5
4
C8 R4 1 RL
2
R3 680 C2 22F C6 100F
R1 D1 22k 1N4001 C4 C7 100nF 220nF
-Vs
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UTC2030
PIN CONNECTION 1 Non inverting input 2 Inverting input 3 -Vs 4 Output 5 +Vs
LINEAR INTEGRATED CIRCUIT
ELECTRICAL CHARACTERISTICS(Refer to the test circuit,Vs=16V,Ta=25C)
PARAMETER
Supply Voltage Quiescent drain current Input bias current Input offset voltage Input offset current
SYMBOL
Vs Id Ib Vos Ios
TEST CONDITIONS
MIN
6
TYP
50 0.2 2 20
MAX
18 80 2 20 200
UNIT
V mA A mV nA
Vs=16v d=0.5%, Gv=26dB f=40 to 15kHz RL=4 RL=8 Po=15W, RL=4
Output power Power bandwidth Slew rate Open loop voltage gain Closed loop voltage gain Total Harmonic distortion
Po BW SR Gvo Gvc d
15 10
18 12 100 8 80 26 0.08 0.03 0.5 0.03 26.5
W W kHz V/sec dB dB % % % %
f=1kHz 25.5 Po=0.1 to 14W, RL=4 f=40Hz to 15kHz Po=0.1 to 14W, RL=4 f=1kHz Po=0.1 to 9W, RL=8 f=40Hz to 15kHz Po=4W, RL=4 f2-f1=1kHz f2=14KHz, f1=15kHz B=curve A B= 22Hz to 22kHz RL=4, Rg=10k, B=curve A Po=15W Po=1W
Total Harmonic distortion Second order CCIF intermodulation distortion Third order CCIF intermodulation distortion Input noise voltage Input noise current Signl to Nois rtio
d d2
d3
0.08
%
2 3 106 94
10
V V dB dB
S/N
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UTC2030
(continued)
LINEAR INTEGRATED CIRCUIT
SYMBOL TEST CONDITIONS
open loop, f=1kHz RL=4, Gv=26dB Rg=22k, f=100Hz
PARAMETER
Input Resistance (pin 1) Supply Voltage rejection Thermal Shut-down junction temperature
MIN
0.5
TYP
5 54 145
MAX
UNIT
M dB
C
TEST CIRCUITS
+Vs
C5 220F C3 100nF D1 1N4001
Vi
C1 1F
1
R3 22k
5 UTC2030 3
R1 13k D1 1N4001 C6 220F C4 C7 100nF 220nF
4
R4 1 RL
2
R3 680 C2 22F
-Vs
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UTC2030
LINEAR INTEGRATED CIRCUIT
+Vs
220F 1N4001
0.1F
Vi
22F
100k 2.2F
1 UTC2030
5 4
2200 RL=4 C7 220nF
100k
2
100k
3
100k
R4 1 1N4001
4.7k 2.2F
Fig. 1 Single supply amplifier
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F
4
UTC2030
Fig.2 Open loop frequency response
Gv (dB)
140
LINEAR INTEGRATED CIRCUIT
Fig.3 Output power vs. Supply voltage
Phase
180
Phase
100 90
Po (W)
18 Gv=26dB d=0.5% f=40 to 15kHz
15
60
0
12
RL=4
Gain
20 9 RL=8
-20
6
-60
3 1 10 2 10 3 10 4 10
Frequency (Hz)
5 10
6 10
7 10
22
24
26
28
Vs (V)
30
32
Fig.4 Total harmonic distortion vs. output power
d (%)
2 10
Fig.5 Two tone CCIF intermodulation distortion
d (%)
2 10
Po (W)
1 10
Gv=26dB
1 10
0 10
Vs=32V RL=8 f=15kHz Vs=28V RL=4 f=1kHz
0 10
Vs=32V Po=4W RL=4 Gv=26dB Order (2f1-f2) Order (2f2-f1)
-1 10
-1 10
-2 10
-2 10
-1 10
0 10
1 10
2 10
-2 10
1 10
2 10
3 10
4 10
5 10
Po (W)
Frequency (Hz)
Fig.6 Large signal frequency response
30
Fig.7 Maximum allowable power dissipation vs. ambient temperture
Ptot (W)
30
Vo (Vp-p)
25
Vs=15V RL=8
25
20
Vs=15V RL=4
20
ea eh init inf g v in h a /W ink ats 5 h e ty = 2 R
10
10
5 1 10 2 10 3 10 4 10
5 -50 0 50 100 150 200
Frequency (kHz)
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15
15
a Rt tsin h= k h 4 av he /W ing a ts R t in k h= ha v 8 /W ing
he
ts i nk
Tamb ()
5
UTC2030
LINEAR INTEGRATED CIRCUIT
+Vs
C3 0.22 F C5 220F /40V
Vi
1
R3 56k
1N4001
C1 2.2F
R1 56k
R6 1.5
BD908
5
C6 0.22 F
UTC2030 3
4
1N4001
C8 2200F
C2 22 F
R2 56k
2
R8 1 RL=4
R5 R4 3.3k 30k C4 10F R7 1.5
BD907 C7 0.22F
Fig. 8 Single supply high power amplifier(UTC2030+BD908/BD907)
TYPICAL PERFORMANCE OF THE CIRCUIT OF FIG. 8
PARAMETER
Supply Voltage Quiescent drain current
SYMBOL
Vs Id
TEST CONDITIONS
Vs=32V d=0.5%,RL=4 f=40Hz to 15kHz,Vs=32V d=0.5%,RL=4 f=40Hz to 15kHz,Vs=28V d=0.5%,f=1kHz, RL=4,Vs=32V d=0.5%,RL=4 f=1kHz,Vs=28V f=1kHz Po=20W,f=1kHz Po=20W,f=40Hz to 15kHz Gv=20dB,Po=20W, f=1kHz,RL=4 RL=4,Rg=10k B=curve A,Po=25W RL=4,Rg=10k B=curve A,Po=25W
MIN
TYP
28 50 32 26
MAX
36
UNIT
V mA
Output power
Po
W 35 28 19.5 20 8 0.02 0.05 890 20.5 dB V/sec % % mV
Voltage Gain Slew Rate Total harmonic distortion Input sensitivity
Gv SR d Vi
Signal to Noise Ratio
S/N
108 100
dB
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UTC2030
Fig. 10 Output power vs. supply voltage
Po (W) 25
LINEAR INTEGRATED CIRCUIT
Fig. 11 Total harmonic distortion vs. output power
d (%) Vs=32V RL=4 Gv=20dB 0 10
20
15 -1 10 f=15kHz 10 f=1kHz 5 22 24 26 28 30 Vs (V) 32 -2 10
-1 10
0 10
1 10
Po (W)
Fig. 12 Output power vs. Input level
Po (W) 20 Ptot (W) 20
Fig. 13 Power dissipation vs. output power
Gv=26dB
15 15
Complete Amplifier
Gv=20dB
10 10 BD908/ BD907
UTC2030 5 5
0 100 250 400 550 700
Vi (mV)
0 0 8 16 24 32 Po (W)
+Vs
C5 100F C3 100nF D1 1N4001
Vi
C1 1F
1
R3 22k
5 UTC2030 3
R5
4
C8 R4 1 RL
2
R3 680 C2 22F C6 100F
R1 D2 22k 1N4001 C4 C7 100nF 220nF
-Vs
Fig. 14 Typical amplifier with split power supply
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UTC2030
LINEAR INTEGRATED CIRCUIT
Vs+
C6 100F C1 2.2F C7 100nF
1 2
5
C8 0.22 F R8 1
IN
R1 22k
UTC2030
4
3
R3 22k C4 22F R4 680 R7 22k
RL 8
1
R2 22k
5
C9 0.22 F R9 1
UTC2030
4
2
3
R5 22k C5 22F
Vs-
C2 100F
C3 100nF
R6 680
Fig. 16 Bridge amplifier with split power supply(Po=34W,Vs+=16V,Vs-=16V)
Multiway speaker systems and active boxes
Multiway loudspeaker systems provide the best possible acoustic performance since each loudspeaker is speciailly designed and optimizied to handle a limited range of frequencies.Commonly,these loudspeaker systems divide the audio spectrum two or three bands. To maintain a flat frequency response over the Hi-Fi audio range the bands cobered by each loudspeaker must overlap slightly.Imbalance between the loudspeakers produces unacceptable results therefore it is important to ensure that each unit generates the correct amount of acoustic energy for its segmento of the audio spectrum.In this respect it is also important to know the energy distribution of the music spectrum to determine the cutoff frequencies of the crossover filters(see Fig. 18).As an example,1 100W three-way system with crossover frequencies of 400Hz and 3khz would require 50W for tthe woofer,35W for the midrange unit and 15W for the tweeter. Both active and passive filters can be used for crossovers but active filters cost significantly less than a good passive filter using aircored inductors and non-electrolytic capacitors.In addition active filters do not suffer from the typical defects of passive filters: --Power less; --Increased impedance seen by the loudspeaker(lower damping) --Difficuty of precise design due to variable loudspeaker impedance.
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UTC2030
LINEAR INTEGRATED CIRCUIT
Obviously, active crossovers can only be used if a power amplifier is provide for each drive unit.This makes it particularly interesting and economically sound to use monolithic power amplifiers. In some applications complex filters are not realy necessary and simple RC low-pass and high-pass networks(6dB/octave) can be recommended. The result obtained are excellent because this is the best type of audio filter and the only one free from phase and transient distortion. The rather poor out of band attenuation of single RC filters means that the lodspeaker must operate linearly well beyond the crossover frequency to avoid distortion. A more effective solution,named "Active power Filter" by SGS is shown in Fig. 19.
The proposed circuit can realize combined power amplifiers and 12dB/octave or 18dB octave high-pass or lowpass filters. In practive, at the input pins amplifier two equal and in-phase voltages are available, as required for the active filter operations. The impedance at the Pin(-) is of the order of 100,while that of the Pin (+) is very high, which is also what was wanted.
Fig. 18 Power distribution vs. frequency
100
Fig. 19 Active power filter
80
IEC/DIN NOISE SPECTRUM FOR SPEAKER TESTING
C1 C2 C3
Morden Music Spectrum
Vs+ RL
60
R1 R2
40
R3
3.3k
Vs100
20
0 1 10 2 10 3 10 4 10 5 10
The components values calculated for fc=900Hz using a Bessel 3rd Sallen and Key structure are: C1=C2=C3=22nF,R1=8.2K,R2=5.6K,R3=33K. Using this type of crossover filter, a complete 3-way 60W active loudspeaker system is shown in Fig. 20. It employs 2nd order Buttherworth filter with the crossover frequencies equal to 300Hz and 3kHz. The midrange section consistors of two filters a high pass circuit followed by a low pass network.With Vs=32V the output power delivered to the woofer is 25W at d=0.06%( 30W at d=0.5%).The power delivered to the midrange and the tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and impedance(RL=4 to 8). It is quite common that midrange and tweeter speakers have an efficiency 3dB higher than woofers.
Musical instruments amplifiers
Another important field of application for active system is music. In this area the use of several medium power amplifiers is more convenient than a single high power amplifier, and it is also more reliable. A typical example(see Fig. 21) consist of four amplifiers each driving a low-cost, 12 inch loudspeaker. This application can supply 80 to 160W rms.
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UTC2030
LINEAR INTEGRATED CIRCUIT
Transient inter-modulation distortion(TIM)
Transient inter-modulation distortion is an unfortunate phenomena associated with negative-feedback amplifiers. When a feedback amplifier receives an input signal which rises very steeply, i.e. contains high-frequency components, the feedback can arrive too late so that the amplifiers overloads and a burst of inter-modulation distortion will be produced as in Fig.22.Since transients occur frequently in music this obviously a problem for the designed of audio amplifiers. Unfortunately, heavy negative feedback is frequency used to reduce the total harmonic distortion of an amplifier, which tends to aggravate the transient inter-modulation(TIM situation.)The best known
Vs+
F 0.22 F
Low-pass 300Hz
IN
680O 1F 22k 22k
1
18nF
5
UTC2030
1N4001
2200
1.5
BD908
4
0.22 F 2200F
33nF
2
100F
3
22k
BD907 1N4001 0.22 F 100 1.5 4
3.3k
1
Woofer
Vs+
Band-pass 300Hz to 3kHz
0.1F 0.1F 22k 22k
0.22F
1N4001
1
18nF
5
UTC2030
4
0.22 F 1
220F
3.3k
6.8k
2
3.3nF
3
1N4001
100F
2.2k
Midrange
100
Vs+
0.22F 1N4001
Vs+
High-pass 3kHz
0.1F 0.1F
1
22k
5
UTC2030
22k
4
1O F
100F
12k
2
3
1N4001
F
100
22k
47F 2.2k
0.22
High-pass 3kHz
Tweeter
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100
8
8
10
UTC2030
Fig.21 High power active box for musical instrument
LINEAR INTEGRATED CIRCUIT
Fig.22 Overshoot phenomenon in feedback amplifiers
20 to 40W Amplifier
V4 INPUT V1
FEEDBACK PATH
PRE AMPLIFIER
V2
V3
POWER AMPLIFIER
OUTPUT V4
20 to 40W Amplifier
V1
20 to 40W Amplifier
V2
20 to 40W Amplifier
V3 V4
method for the measurement of TIM consicts of feeding sine waves superimposed onto square wavers,into the amplifier under test.The output spectrum is then examined using a spectrum analyser and compared to the input.This method suffers from serious disadvantages:the accuracy is limited, the measurement is a tather delicate operation and an expensive spectrum analyser is essential.A new approach (see Technical Note 143(Applied by SGS to monolithic amplifiers measurement is fast cheap,it requires nothing more sophisticated than an oscilloscope-and sensitive-and it can be used down to the values as low as 0.002% in high power amplifiers. The "inverting-sawtooth" method of measurement is based on the response of an amplifier to a 20KHz sawtooth waveform.The amplifier has no difficulty following the slow ramp but it cannot follow the fast edge.The output will follow the upper line in Fig.23 cutting of the shade area and thus increasing the mean level.If this output signal is filtered to remove the sawtooth,direct voltage remains which indicates the amount of tIM distortion, although it is difficult to measure because it is indistingishable from the DC offset of the amplifier.This problem os neatly avoided in the IS-TIM method by periodically inverting the sawtooth waveform at a low audio frequency as shown in Fig.24.Inthe case of the sawtooth in Fig. 25 the means level was increased by the TIM distortion, for a sawtooth in the other direction the opposite is ture.
SR(V/s)
m2 m1
Input Signal
Filtered Output Siganal
Fig.23 20kHz sawtooth waveform Fig.24 Inverting sawtooth waveform
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UTC2030
LINEAR INTEGRATED CIRCUIT
The result is an AC signal at the output whole peak-to-peak value is the TIM voltage,which can be measured easily with an oscilloscope.If the peak-topeak value of the signal and the peak-to-peak of the inverting sawtooth are measured,the TIM can be found very simply from:
TIM =
VOUT * 100 Vsawtooth
Fig. 25 TIM distortion Vs. Output Power
1 10 2 10
Fig. 26 TIM design diagram(fc=30kHz) SR(V/ )
TIM(%)
0 10
UTC2030 BD908/907 Gv=26dB Vs=32V RL=4
-1 10
RC Filter fc=30kHz
0 10
-2 10
-1 10
0 10
1 10
Po(W)
2 10
-1 10
-1 10
TI M =0 .0 TI 1% M =0 .1 TI % M =1 %
0 10
In Fig.25 The experimental results are shown for the 30W amplifier using the UTC2030 as a driver and a low-cost complementary pair.A simple RC filter on the input of the amplifier to limit the maxmium signal slope(SS) is an effective way to reduce TIM. The Digram of Fig.26 originated by SGS can be used to find the Slew-Rate(SR) required for a given output power or voltage and a TIM design target. For example if an anti-TIM filter with a cutoff at 30kHz is used and the max.Peak to peak output voltage is 16V then, referring to the diagram, a Slew-Rate of 6V/s is necessary for 0.1% TIM. As shown Slew-Rates of above 10V/s do not contribute to a further reduction in TIM. Slew-Rates of 100V/s are not only useless but also a disadvantage in Hi-Fi audio amplifiers because they tend to turn the amplifier into a radio receiver.
Power Supply
Using monolithic audio amplifier with non regulated supply correctly.In any working case it must provide a supply voltage less than the maximum value fixed by the IC breakdown voltage. It is essential to take into account all the working conditions, in particular mains fluctuations and supply voltage variations with and without load.The UTC2030(Vsmax=32V) is particularly suitable for substitution of the standard IC power amplifiers(with Vsmax=28V) for more reliable applications. An example, using a simple full-wave rectifier followed by a capacitor filter, is shown in the table and in the diagram of Fig.27. A regulated supply is not usually used for the power output stages because of its dimensioning must be done taking into account the power to supply in signal peaks.They are not only a small percentage of the total music signal, with consequently large overdimensioning of the circuit. Even if with a regulated supply higher output power can be obtained(Vs is constant in all working conditions),the additional cost and power dissipation do not usually justify its use.using non-regulated supplies,there are fewer designe restriction.In fact,when signal peaks are present, the capacitor filter acts as a flywheel supplying the required energy.
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RC Filter fc=30kHz
1 10
1 10
2 10
Vo(Vp-p)
12
UTC2030
LINEAR INTEGRATED CIRCUIT
In average conditions,the continuous power supplied is lower.The music power/continuous power ratio is greater in case than for the case of regulated supplied,with space saving and cost reduction.
Fig.27 DC characteristics of 50W non-regulated supply Vo(V)
26
Ripple (Vp-p)
24 Ripple 22 2 20 4
220V Vo
3300F
Vout
18
0
0
0.4
0.8
1.2
1.6
2.0
Io(A)
Mains(220V)
Secondary voltage
23.0V 22.1V 21.1V 19.2V 17.3V 16.3V 15.3V Io=0 34.5V 33.1V 31.7V 29.0V 25.9V 24.5V 23.0V
DC output Voltage(Vo)
Io=0.1A 33.6V 32.2V 30.8V 28.0V 25.2V 23.8V 22.4V Io=1A 30.0V 28.6V 27.3V 24.8V 22.2V 20.8V 19.4V
+20% +15% +10% -10% -15% -20%
Short Circuit Protection
The UTC2030 has an original circuit which limits the current of the output transistors.This function can be considered as being peak power limiting rather than simple current limiting.It reduces the possibility that the device gets damaged during an accidental short circuit from AC output to Ground.
Thermal Shut-Down
The presence of a thermal limiting circuit offers the following advantages: 1).An overload on the output (even if it is permanent),or an above limit ambient temperture can be easily supported since the Tj can not be higher than 150C 2).The heat-sink can have a smaller factor of safety compared with that of a convential circuit,There is no possibity of device damage due to high junction temperature increase up to 150, the thermal shut-down simply reduces the power dissipation and the current consumption.
--
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UTC2030
APPLICATION SUGGESTION
LINEAR INTEGRATED CIRCUIT
The recommended values of the components are those shown on application circuit of Fig.14. Different values can be used.The following table can help the designer. Component R1 R2 R3 R4 Recommended value 22K 680 22K 1 Purpose Closed loop gaon setting. Closed loop gaon setting. Non inverting input biasing Frequency stacility Large than recommended value Increase of Gain Decrease of Gain Large than recommended value Decrease of Gain Increase of Gain
R5 C1 C2 C3,C4 C5,C6 C7 C8 D1,D2
3R2 1F 22F 0.1F 100F 0.22F 1/(2*B*R1) 1N4001
Increase of input Decrease of input impedance impedance Danger of oscillation at high frequencies with inductive loads. Upper frequency Poor high frequencies Dange of oscillation attenuation cutoff Input DC decoupling Increase of low frequencies cutoff Inverting DC Increase of low decoupling frequencies cutoff Supply voltage Dange of oscillation bypass Supply voltage Dange of oscillation bypass Frequency stability Larger bandwidth Upper frequency smaller bandwidth Larger bandwidth cutoff To protect the device against output voltage spikes.
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